KR20140015528A - Dc-dc converter with modular stages - Google Patents

Abstract

The device for power conversion comprises a converter having an input terminal and an output terminal, the converter including an adjusting circuit, the adjusting circuit including an inductance and switching elements coupled to the inductance, the switching element Perform a switch control between switching configurations, wherein said regulating circuit maintains an average DC current through said inductance, and comprises a switching network having an input port and an output port, said switching network comprising charge storage elements. And switching elements coupled to the charge storage elements, wherein the switching elements perform switch control between switch configurations in a switch configuration, the switching elements forming an array of charge storage elements, and storing charge The element is connected to the input port and the output of the switching network. In is charged through one of the ports, yet another configuration, the switching elements form an array of charge storage elements.

Description

DC-DC converter with modular steps {DC-DC CONVERTER WITH MODULAR STAGES}

TECHNICAL FIELD The present invention relates to power supplies, and more particularly to power converters.

The plurality of power converters includes at least one capacitor and switches for example used in portable electronics and consumer electronics. Switched mode power converters use a switching network to regulate the output current or output voltage by switching energy storage components (eg, inductors and capacitors) in other electrical configurations. Switched capacitor converters are mainly switch-mode power converters that use capacitors to convert energy. Within such converters, the number of switches and capacitors increases as the transformation ratio increases. Switches in a switching network are typically active devices implemented as transistors. The switching network may be integrated into single or multi monolithic semiconductor substrates or may be formed using discrete devices.

Typical DC-DC converters perform voltage conversion and output regulation. However, these two functions are capable of separating the two functions into two specialized stages, i.e. separate control stages, such as a switching stage and regulating circuit, such as a switching network. Do. The converting step is to convert the voltage to another voltage, while the adjusting step is to ensure that the current and / or voltage output of the converting step is maintained at the desired characteristics.

For example, referring to FIG. 1, the switching network 12A of the converter 10 has an input terminal connected to a voltage source 14. The input end of the regulating circuit 16A is then connected to the output end of the switching network 12A. The load 18A is then connected to the output of the regulation circuit 16A. Power flows in the direction indicated by the arrows between voltage source 14 and load 18A. Such a converter is disclosed in US Pub. No. 2009/0278520, filed May 8, 2009, the configurations of which are incorporated herein by reference.

It is an object of the present invention to provide a DC-DC converter with a modular step cross reference for related applications.

In one aspect, the invention features a device for power conversion. Such a device includes a converter having an input terminal and an output terminal. The converter includes a regulating circuit, the regulating circuit including an inductance and switching elements coupled to the inductance. The switching elements perform switch control between switching configurations. The regulating circuit maintains an average DC current through the inductance. The converter also includes a switching network having an input port and an output port. The switching network includes charging storage elements and switching elements connected to the charging storage elements. The switching elements perform switch control between switch configurations in one switch configuration. The switching elements form a first array of charge storage elements, and the charge storage element is charged through one of the input port and the output port of the switching network. Within another configuration, the switching elements form a second array of charge storage elements, wherein the charge storage elements are discharged through one of the input port and the output port of the switching network. The switching network and the converter satisfy at least one of the following configurations. (1) said regulating circuit is connected between said switching network and said output terminal of said converter, said switching network being a thermally charged switching network, and (2) said regulating circuit is an output of said converter and said switching network. Connected between the terminals, wherein the switching network is a multiphase switching network or the regulating circuit is multi-phase, the switching network and the regulating circuit are bidirectional, and (3) the regulating circuit is an input terminal of the converter. And an input port of the switching network, wherein the switching network is a thermally charged switching network, and (4) the regulating circuit is connected between an input terminal of the converter and an input port of the switching network; The switching network is multiphase switching. Network or the regulating circuit is polyphase, the switching network and the regulating circuit are bidirectional, (5) the switching circuit is connected between the regulating circuit and an additional regulating circuit, or (6) the regulating circuit is It is connected between the switching network and the additional switching network.

In an embodiment of the invention, the switching network comprises a reconfiguration switching network, the switching network comprising a multi-phase switching network.

Another embodiment of the invention includes the regulating circuit comprising a bidirectional regulating circuit, the regulating circuit comprising a multi-phase regulating circuit, the regulating circuit being bidirectional, comprising a switch mode power converter, The regulating circuit is bidirectional and includes a resonant power converter, the regulating circuit is connected to an output of the switching network, the regulating circuit is connected between an output terminal of the converter and the switching network, the switching network Is a thermally charged switching network.

In another embodiment of the present invention, the regulating circuit is connected between the output terminal of the converter and the switching network, wherein the switching network is a polyphase switching network or the regulating circuit is polyphase, the switching network and the regulating circuit. Is bidirectional.

In another embodiment of the invention, the regulating circuit is connected between the input terminal of the converter and the input port of the switching network, wherein the switching network is a thermally charged switching network.

In another embodiment, the regulating circuit is connected between an input terminal of the converter and an input port of the switching network, wherein the switching network is a polyphase switching network or the regulating circuit is polyphase and the switching network and the regulating The circuit is bidirectional.

In still other embodiments the switching circuit is connected between the regulating circuit and the further regulating circuit, wherein the regulating circuit is connected between the switching network and the further switching network.

In a further embodiment of the invention, the switching circuit is configured as an AC switching circuit. This embodiment of the present invention also includes a power-factor correction circuit connected to the AC switching network. In this embodiment of the present invention, the power factor improving circuit is connected between the AC switching network and the control circuit.

In another aspect, the invention features a device comprising a converter having an input terminal and an output terminal. The converter comprises a switching network having an input port and an output port. Such a switching network includes charging storage elements, which switching elements are connected to the charging storage elements. The switching elements are controlled to arrange the charge storage elements in a selected configuration. In at least one configuration, the switching elements form a first group of charge storage elements to discharge the charge storage elements through an output port of the switching network. In another configuration, the switching elements form a second group of charge storage elements to charge the charge storage elements through an input port of the switching network. The converter also includes a bidirectional regulating circuit connected between at least one of the input terminal of the converter and the input port of the switching network and between the output terminal of the converter and the output port of the switching network.

In some embodiments, the switching network comprises a polyphase switching network.

In addition, the bidirectional regulation circuit included in the embodiments includes a buck / boost circuit, and the bidirectional regulation circuit includes a divided pi circuit.

In another aspect, the invention is characterized by a converter having an input terminal and an output terminal. The converter comprises a switching network having an input port and an output port, charging storage elements, and switching elements connected to the charging storage elements for arranging the charging storage elements of any one of a plurality of configurations.

In one configuration, the switching elements form a first group of charge storage elements to discharge the charge storage elements through an output port of the switching network. In another configuration, the switching elements form a second group of charge storage elements for charging the charge storage elements through an input port of the switching network. The converter provides a stepped-up voltage and further comprises a regulating circuit connected between the output terminal of the converter and the output port of the switching network.

In another aspect, the invention features an apparatus having an input terminal and an output terminal, the apparatus having a switching network having an input port and an output port, charging storage elements, and switching elements connected to the charging storage elements. have. The switching elements can control the switching elements arranged in a plurality of configurations. In one configuration, the switching elements form a first group of charge storage elements to discharge the charge storage elements through an output port of the switching network. In another configuration, the switching elements form a second group of charge storage elements to charge the charge storage elements through an input port of the switching network. The apparatus further includes a source control circuit coupled between the input terminal of the converter and the input port of the switching network.

Some embodiments also further include a load regulation circuit connected between the output terminal of the converter and the output port of the switching network.

In another aspect, the invention features a fabrication comprising multiple switching networks and regulating circuits with inputs and outputs to allow modular interconnection for the assembly of a DC-DC converter.

In some embodiments, at least one switching network comprises a switched capacitor network. Among them such a switched capacitor network comprises a switched capacitor network which is adiabaticly charged. These embodiments also include the thermally charged switched capacitor network comprising a cascade multiplayer. In some of these embodiments, the cascade multiplayer is driven by complementary clock current sources.

In another embodiment, the at least one regulating circuit comprises a linear regulator.

Embodiments of the invention also include the DC-DC converter including series connected switched capacitor networks, the DC-DC converter including multiple regulating circuits sharing a common switching network.

These and other features of the present invention will become apparent from the following detailed description and the accompanying drawings.

The apparatus for power conversion of the present invention includes a converter having an input terminal and an output terminal, the converter including a regulating circuit, the regulating circuit including switching elements connected to inductance and inductance, the switching elements being switching configurations. Performing a switch control between the control circuitry, the regulating circuit maintains an average DC current through inductance, and comprises a switching network having an input port and an output port, the switching network being connected to the charging storage elements and the charging storage elements. Elements, wherein the switching elements perform switch control between the switch configurations in one switch configuration, the switching elements forming an array of charging storage elements, the charging storage element being one of the input and output ports of the switching network. Charging through one, and within another configuration, switching elements Silver may form an array of charge storage elements.

1 is a diagram illustrating a DC-DC converter in which a regulating circuit and a switching network are separated.
1A is a diagram illustrating a bidirectional version of FIG. 1.
2-4 show a DC-DC converter with alternative configurations of regulating circuits and switching networks.
FIG. 5 is a diagram illustrating a specific embodiment of the power converter shown in FIG. 4.
FIG. 6 shows an embodiment of the invention with multiple regulating circuits. FIG.
7 is a diagram illustrating an RC circuit.
8 is a diagram illustrating a model of a switched capacitor DC-DC converter.
9A and 9B are diagrams illustrating a series-parallel SC converter operating in a charge phase and a discharge phase, respectively.
10 is a diagram illustrating a series pumped symmetric cascade multiplier with diodes.
FIG. 11 shows a parallel pumped symmetric cascade multiplier with diodes.
FIG. 12 is a diagram illustrating charge pump signals. FIG.
FIG. 13 is a diagram illustrating a two-phase symmetric series pumped cascade multiplayer with switches. FIG.
14 shows a two-phase symmetric parallel pumped cascade multiplayer with switches.
FIG. 15 is a diagram illustrating four different cascade multiplayers according to half-wave versions.
16 is a diagram showing the output impedance of a switched-capacitor converter as a frequency function.
FIG. 17 is a diagram illustrating a particular embodiment of the DC-DC converter shown in FIG. 1A with a switching network in which radio waves are adiabatically charged.
FIG. 18 shows the DC-DC converter shown in FIG. 17 during phase A. FIG.
FIG. 19 shows the DC-DC converter shown in FIG. 17 during phase B. FIG.
20 illustrates various waveforms associated with a 4: 1 adiabatically charged converter.
FIG. 21 is a diagram showing adiabatic charging of steps connected in series. FIG.
FIG. 22 is a diagram illustrating a specific embodiment of the power converter shown in FIG. 21.
FIG. 23 illustrates a rectified AC voltage using a reconfigured switched capacitor stage. FIG.
24 shows an AC-DC power converter architecture.
FIG. 25 is a diagram showing a specific embodiment of the AC-DC converter shown in FIG. 24.
FIG. 26 shows the AC-DC converter shown in FIG. 25 during the positive portion of the AC cycle.
FIG. 27 shows the AC-DC converter shown in FIG. 25 during the negative portion of the AC cycle.
FIG. 28 illustrates an AC-DC converter architecture with power-factor correction.
29 and 30 are diagrams showing particular embodiments of the DC-DC converter shown in FIG.
31 and 32 are diagrams showing specific embodiments of the DC-DC converter shown in FIG.
33 and 34 show specific embodiments of the DC-DC converter shown in FIG. 2.
35 and 36 illustrate a specific embodiment of the DC-DC converter shown in FIG. 4.

: Transformative Integrated Power Solution

) 제공한다. 이와 같이, 도 1에 도시한 구성은 적어도 하나의 조절 회로들 16A을 구비한 적어도 하나의 스위칭 네트워크 12A를 구성하기 위한 다양한 방법들 중 단지 하나를 나타낸다. 도 1A는 도 1의 양방향 버전을 나타내는 도면으로, 전력은 화살표들에 의해 나타나는 것과 같이 소스 14로부터 부하 18A로 흐르거나 또는 부하 18A로부터 소스 14로 흐를 수 있다. In an embodiment of the present invention, at least, the switching network and regulating circuit in the multi-stage DC-DC converter can be made essentially modular and can be matched and mixed in many different ways. Describe at least depending on the part about recognition. It is a modified integrated power solution (TIPS) for the assembly of these converters.

: Transformative Integrated Power Solution

) to provide. As such, the configuration shown in FIG. 1 represents only one of various methods for configuring at least one switching network 12A with at least one regulating circuit 16A. 1A is a diagram illustrating the bi-directional version of FIG. 1, wherein power may flow from source 14 to load 18A or from load 18A to source 14 as represented by arrows.

There are two basic elements described in connection with the embodiments of the following switching networks and regulating circuits. Assuming elements of the same type are connected in series, there are a total of four basic building blocks. These are shown in Figures 1-4. An embodiment of the present invention includes at least one of the four basic building blocks shown in FIGS. 1 to 4.

In addition, embodiments of the present invention are “instantiated” regulating circuit 16A in various other ways while the inputs and outputs continue to match a manner that facilitates module assembly of DC-DC converters with various properties. Further consideration is given to the application of object-oriented programming concepts for the design of DC-DC converters by enabling the switching network 12A.

Switching network 12A in various embodiments is illustrated as a switching capacitor network. Among the more useful switched capacitor topologies are Ladder, Dickson, Series-Parallel, Fibonacci and Doubler, all of which can be implemented in adiabatic charging and multiphase networks. A particularly useful switching capacitor network is the adiabatic charging version of a full-wave cascade multiplier. However, adiabatic charging versions can also be used.

In an embodiment of the present invention, changing the charge on the adiabatic capacitor means that the amount of charge is stored in the capacitor as a result of passing charge through the noncapacitive element. A positive adiabatic change in the capacitor charge is considered to be an insulating charge, while a negative adiabatic change in the capacitor charge is considered to be adiabatic discharge. Examples of noncapacitive elements include inductors, magnetic elements, resistors, and combinations thereof.

In some cases, the capacitor may be adiabaticly charged at some time and non-insulated at other times. These capacitors are considered to be adiabaticly charged. Similarly, in some embodiments, the capacitor may be adiabatic discharged at some time and may be discharged in a non-insulated manner at the remaining time. These capacitors are considered to be adiabatic.

Non-insulated charges include all charges that are not adiabatic, and non-insulated discharges include all discharges that are not adiabatic.

An adiabaticly charged switching network used in an embodiment of the present invention is a switching network having at least one capacitor which is adiabaticly charged and adiabaticly discharged. A non-insulated switched network is a switching network rather than an adiabaticly charged switching network.

Regulating circuit 16A is exemplified as any converter capable of regulating the output voltage. For example, buck converters are promising candidates for their high efficiency and speed. Other suitable regulating circuits 16A are boost converters, buck / boost converters, fly-back converters, Cuk converters, resonant converters. converters) and linear regulators.

In an embodiment of the invention, as shown in FIG. 2, source voltage 14 delivers an input to first switching network 12A, for example as a switching capacitor network. The output of the first switching network 12A is a voltage lower than the input voltage provided to the regulating circuit 16A (eg, a buck, boost, or buck / boost converter). Regulating circuit 16A delivers the regulated voltage to another switching capacitor network, second switching network 12B. The high voltage output of the second switching network 12B is applied to the load 18A.

As shown in FIG. 2, embodiments of the present invention may be configured to adjust source 14 or adjust load 18A according to the direction of energy flow.

In another embodiment, as shown in FIG. 3, low voltage source 14 is connected to the input of regulating circuit 16A and the output is passed to the input of switching network 12A to be able to boost to a higher DC value. The output of the switching network is then delivered to load 18A.

As shown in FIG. 3, embodiments of the present invention can be used to adjust source 14 or load 18A depending on the direction of energy flow.

Referring next to FIG. 4, another embodiment of the converter 100 includes a first regulation circuit 300A coupled to an input 102 and a second regulation circuit 300B coupled to an output 104. Between the first regulating circuit 300A and the second regulating circuit 300B is a switching network 200 having an input 202 and an output 204. The switching network includes charge storage elements 210 connected to each other by switches 212. The charge storage elements 210 are divided into a first group 206 and a second group 208.

In some embodiments, the switching network 200 may be a bidirectional switching capacitor network as shown in FIG. 5. The switching capacitor network of FIG. 5 is characterized in that the first capacitor 20 and the second capacitor 22 are configured in parallel. The first switch 24 selectively connects one of the first capacitor 20 and the second capacitor 22 to the first regulating circuit 300A, and the second switch 26 connects one of the first capacitor 20 and the second capacitor 22 to the second regulating circuit 300B. Optionally connect to Both the first switch 24 and the second switch 26 can be operated at high frequencies and can enable adiabatic charging and discharging of the first capacitor 20 and the second capacitor 22.

As shown in FIG. 5, certain embodiments include a two-phase switching network 200. However, other types of switching networks may be used instead.

In another embodiment, as shown in FIG. 6, multiple regulating circuits 16A, 16B, 16C can deliver the output of first switching network 12A to drive multiple loads 18A-18C. For one of the loads 18C, the second switching network 12B is provided between the load 18C and the corresponding regulating circuit 16C and creates a path similar to that shown in FIG. 6 provides an example of a modular configuration method of regulating circuits and switching networks that are easy to match and mix elements to provide flexibility in DC-DC converter configuration.

Switched Capacitor (SC) DC-DC power converters include a network of switches and capacitors. These switches can be used to transfer energy from the input to the output of the SC network by cycling the network through different topology steps. Some converters known as "charge pumps" can be used for high voltage generation of flash and other reprogrammable memories.

에 의해 설명될 수 있다. 정확한 커패시터 전압 V_c(t) 및 전류 i_c(t)는 다음 방정식에 의해 주어진다. 7 shows a capacitor C initially charged to an arbitrary voltage V _c (0). The switch S is closed at t = 0. At this moment, a brief surge of current flows as capacitor C is charged to the final voltage of V _in . The charge rate is a time constant that represents the time it takes for the voltage to increase or decrease within the lie of the final voltage.

It can be explained by. The exact capacitor voltage V _c (t) and current i _c (t) are given by the following equation.

(1.1)

(1.1)

(1.2)

(1.2)

The energy loss that occurs while charging the capacitor can be found by calculating the energy dissipated in resistor R.

(1.3)

(1.3)

The equation can be further simplified by replacing the expressions for i _c (t) from equation (1.2) to equation (1.3), and then calculating the integral.

The equation can be further simplified by replacing the expressions for i _c (t) with equation (1.3) from equation (1.2) and then computing the integral.

If the transistors are allowed to settle (eg t-oo), the total energy loss incurred when charging the capacitor is independent of the resistance value R. In this case, the energy loss is as follows.

The switched capacitor converter is shown in FIG. 8, as shown in FIG. 8, with a finite output resistance Ro, which is considered for power loss that may result from the discharge or charging of the energy conversion capacitors. As one can, it can be modeled as an ideal transformer. This loss is typically consumed by the equivalent series resistance of the capacitors and the ON resistance of the MOSFETs.

The output voltage of the switched capacitor converter is given by

 The operation of switched capacitor converters can be simplified and there are two limited cases where R0 can be easily found. These are called "slowswitching limits" and "fast-switching limits".

)에서, 충전 및 방전 전류들은 대부분 상수 이며, 커패시터들에 삼각형의 AC 리플(ripple)을 야기한다. 따라서, Ro는 MOSFETs 및 캐피시터들의 직렬 저 항들에 민감하지만, 동작 주파수의 기능을 하지 않는다. 이러한 경우, 고속스위칭 제한에서 컨버터 동작의 출력 저항은 기생 저항(parasitic resistance)의 기능을 한다. Fast Switching Limit (

), The charge and discharge currents are mostly constant, causing triangular AC ripple in the capacitors. Thus, Ro is sensitive to the series resistances of MOSFETs and capacitors but does not function as an operating frequency. In this case, the output resistance of the converter operation in the fast switching limit functions as a parasitic resistance.

)은 Reff 에 독립적이 된다. 이러한 에너지 손실을 감소시키기 위한 해결방안은 스위치드 커패시터 네트워 크의 펌프 커패시터들(pump capacitors)의 크기를 증가시키는 것이다.In the low speed switching limit, the switching period Tsw is longer than the RC time constant T of the energy conversion capacitors. In this situation, the overall energy is lost regardless of the resistance of the capacitors and switches. This overall energy loss is due in part to the root mean square (RMS) of the charge and discharge currents as a function of the RC time constant. If the effective resistance Reff of the charging path is reduced (e.g., RC is reduced), the RMS current increases and the total charging energy loss (

) Becomes independent of Reff. A solution to reduce this energy loss is to increase the size of the pump capacitors in the switched capacitor network.

It is desirable for the switching capacitor network to have a common ground, large transformation ratio, low switch stress, low DC capacitor voltage and low output resistance. More useful topologies are among Ladder, Dickson, Series-Parallel, Fibonacci, and Doubler.

One useful converter is a series-parallel switched capacitor. 9A and 9B are diagrams illustrating a series-parallel switched capacitor converter having a charge phase and a discharge phase of 2: 1, respectively. During the charging phase, the capacitors are in series. During the discharge phase, the capacitors are in parallel. In the charging phase, the capacitor voltages V _C1 and V _C2 are added to V ₁ , while in the discharge phase V _C1 And V _C2 are equal to V ₂ . At this time, V ₂ = V _1/2 .

는 180 도 위상 차이가 발생한다. 커플링 커패시터들은 직렬로 펌핑되거나 또는 병렬로 펌핑된다. Other useful topologies are cascade multiplier topologies shown in FIGS. 10 and 11. In both charge pumps, the source is located at V ₁ and the load is located at V ₂ . In these types of charge pumps, packets of charge are pumped along the diode chain as coupling capacitors are successfully charged and discharged. As shown in FIG. 12, the clock signal V _clk including amplitude v _pump and

The 180 degree phase difference occurs. The coupling capacitors are pumped in series or in parallel.

가 된다.It takes n clock cycles for the initial charge to reach the output. Since the charge to the last pump capacitor takes n times more than the charge to the first pump capacitor, the output voltage V ₂ to the converters is the same in both pumping configurations.

.

While the previous topologies are suitable for boosting voltage, they can also be used to reduce the voltage by changing the source and load positions. In this case, the diodes can be replaced with regulating switches such as MOSFETs and BJTs.

The aforementioned cascade multiplayers are half f-wave multipliers in which charge is transmitted during one phase of the clock signal. This causes discontinuities in the input current. These cascade multiplayers can all be converted to full-wave multipliers by connecting two half-wave multiplayers in parallel or by running 180 degrees of phase difference multiplayers. FIG. 13 shows a full-wave symmetric series pumped cascade multiplier version, while FIG. 14 shows a full-wave symmetric parallel pumped cascade multiplayer. plier). Unlike the diodes of half-multiplier, the switches of FIGS. 13 and 14 are bidirectional. As a result of all of these cascade multiplayers, power may flow from source to load or from load to source. Asymmetric multiplayers can be converted to full-wave multiplayers.

15 is four different voltage increasing versions of propagating multiplayer according to corresponding half-wave versions. In addition, N phases can be combined in parallel, and can be operated with 180 degrees / N phase difference to reduce output voltage ripple and increase output power processing capability.

 The basic building blocks of the modular architecture shown in FIGS. 1 to 4 may be connected as independent entities or coupled entities. The switching networks and regulating circuits in this situation are tightly coupled and can reduce or prevent the overall energy loss mechanism of the switching networks via adiabatic charging. Generally, a regul ating circuit is used to control the charging and discharging of the capacitors of the switching network. In addition, the regulating circuit and the output voltage of the entire converter can be regulated in response to an external stimulus. An approach to regulating the output voltage is to control the average DC current of the magnetic storage element.

A desirable feature of the regulating circuit is to limit the RMS current flowing through the capacitors of the switching network. For this purpose, the regulating circuit uses resistors or magnetic storage elements. Unfortunately, resistive devices consume power, so it is desirable to use less. Thus, embodiments of the present invention are described depending on the combination of magnetic storage elements and switches in the regulating circuit. The regulating circuit limits the RMS current by the capacitor current flowing through the magnetic storage element of the regulating circuit with an average DC current. The switches of the regulating circuit can be operated as to maintain the average DC current flowing through the magnetic storage element.

The regulating circuit limits both the RMS charge current and RMS discharge current of at least one capacitor in the switching scheme. A single regulating circuit limits the input or output current of the switching network by sinking and / or sourcing current. There are four basic configurations as shown in FIGS. Assuming power flows from source to load in FIG. 1, regulating circuit 16A can sink both the charge and discharge currents of switching network 12A. In FIG. 3, the regulating circuit 16A can source both the charging and discharging currents of the switching network 12A. In FIG. 4, the regulating circuit 300A can source the charging current of the switching network 200, and the regulating circuit 300 B can sink the charging current of the same switching network 200, and vice versa. In FIG. 2, the regulating circuit 16A can source both the charge and discharge currents of the switching network 12B, while also sinking both the charge and discharge currents of the switching network 12A. In addition, if both switching networks and regulating circuits are capable of power flow in both directions, bidirectional power flow is possible (source to load and source to load).

In one embodiment, it depends on at least partially adiabaticly charged propagation cascade multiplayers. Cascade multiplayers are preferred for switching networks because of their high fast switching limit impedance, ease of voltage scale enhancement, and low switch stress.

로 펌핑된다. 그러나, 만일 커플링 커패시터들이 클록 전류 소스 i_clk &

로 대신 펌핑된다면, 커플링 커 패시터 내의 RMS 충전 및 방전 전류는 제한될 것이다. 이러한 경우, 저속 스위칭 제한으로 동작하면, 커패시 트들은 적어도 부분적으로 단열 충전되며, 스위치드 커패시터 컨버터와 관련된 손실

이 제거되지는 않지만 감소하게 된 다. 이것은 고속 스위칭 제한으로 출력 임피던스를 낮추는데 효율적이다. 단열 동작을 묘사한 도 16의 점선 으로된 블록들에 의해 보여지는 바와 같이, 전체 단열 충전에서, 출력 임피던스는 스위칭 주파수의 기능을 더 이상 하지 않는다. In cascade multiplayers, coupling capacitors are typically clock voltage source V _clk &

Pumped into. However, if the coupling capacitors are clock current source i _clk &

If pumped instead of furnace, the RMS charge and discharge current in the coupling capacitor will be limited. In this case, when operating with a slow switching limit, the capacitors are at least partially adiabaticly charged and the losses associated with the switched capacitor converter.

This is not eliminated but reduced. This is efficient at lowering the output impedance due to the fast switching limit. As shown by the dashed blocks in FIG. 16 depicting the adiabatic operation, in full adiabatic charging, the output impedance no longer functions as a switching frequency.

With the same conditions, adiabaticly charged switched capacitor converters can operate with much lower switching frequency than conventionally charged switched capacitor converters, but may also have higher efficiency. Conversely, adiabaticly charged switched capacitor converters have the same efficiency as conventionally charged switched capacitor converters and operate at the same frequency but must have smaller coupling capacitors that are much smaller, for example between 4 and 10 times.

는 조절 회로 16A 및 네 개의 스 위치들에 의해 동작된다. 출력 커패시터 Co는 스윙(swing)을 위해 Vx를 허용함으로써 제거될 수 있다. 이러 한 예로, 조절 회로 16A는 작은 AC 리플을 갖는 항등 소스(constant source)로서 동작하는 부스트 컨버터(b oost converter)가 된다. 비용량성 입력 임피던스를 구비한 어떤한 파워 컨버터는 단열 동작을 허락할 수 있다. 비록 스위치 모드 파워 컨버터들이 고효율성 때문에 주요 후보들이 될지라도, 선형 레귤레이터들(linea r regulators) 또한 실현 가능하다. FIG. 17 is a diagram illustrating a step-down converter configuration having the architecture shown in FIG. 1A. However, in this embodiment, the switching network 12A is adiabaticly charged using the regulating circuit 16A. Clock Current Sources i _clk &

Is operated by regulating circuit 16A and four switches. The output capacitor Co can be removed by allowing Vx for swing. In this example, regulating circuit 16A is a boost converter that operates as a constant source with small AC ripple. Any power converter with a non-capacitive input impedance can allow for adiabatic operation. Although switch-mode power converters are key candidates for their high efficiency, linear regulators are also feasible.

In operation, when the switches marked 1 close the capacitors C ₄ , C ₅ And C ₆ are charged, while capacitors C ₁ , C ₂ and C ₃ are discharged. Similarly, the switches marked 2 have a complementary effect. In the first topology phase (phase A), all switches marked 1 are closed and all switches marked 2 are equal to 18 opened. Similarly, the second topology phase (phase B) is the same as in FIG. 19 where all switches marked 2 are closed and all switches marked 1 are open. In an embodiment of the invention, regulating circuit 16A limits the RMS charge and discharge current of each capacitor. For example, capacitor C ₃ is discharged through the filter inductor of regulating circuit 16A during phase A, while capacitor C ₃ is charged through the filter inductor of regulating circuit 16A during phase B, demonstrating a clear thermal isolation concept. In addition, all active configurations are implemented with switches, allowing the converter to handle power in both directions.

Representative node voltages and currents are as shown in FIG. 20. There is a small amount of distortion at the rising and falling edges of the two illustrated currents I _P1 and I _P2 , but in general, the currents are similar to two clocks that are 180 degrees out of phase. In general, adiabatic charging occurs in cascade multiplayer at least when one end of the switch stack does not load capacitance, so in the case of an embodiment of the present invention, node Vx is controlled by regulating circuit 16A. Decompression

The modular architecture with the basic building blocks shown in FIGS. 1-4 further extends the range of applications such as high voltage DC, AC-DC, buck-boost and multiple output voltages. It can be extended to cover wider. Each of these applications includes separate conversion and adjustment functions. Expansion of the architecture can also incorporate adiabatic charged switched capacitor converters.

In a plurality of switched capacitor converters, the number of capacitors and switches increases linearly with the transformation ratio. In addition, a large transformer ratio requires a plurality of capacitors and switches. Instead, a large transformer ratio can be achieved by connecting a plurality of low gain steps shown in FIG. 21 in series. The transformer ratio of the entire switch capacitor stack (V _in / V _x ) is:

(2 .1)

(2 .1)

The most disadvantage of the series in which the configurations are loaded is the voltage strength in the preceding steps

 stresses) are much higher than later steps. This will generally require steps with different voltage ratings and magnitudes.

The adiabatic charging of the series-connected switched network described above is then generated only if the switching network is controlled by the charging and discharging currents of the above-mentioned steps. Thus, switched capacitor stages, such as single phase series-parallel switch ed-capacitor converters, using electromagnetically switched capacitor converters in the preceding stages or having a magnetic based on input filters. It is preferable to precede them.

FIG. 22 is a diagram illustrating a converter with two serially connected switching networks having the architecture shown in FIG. 21. Switching networks 12A and 12D are two-phase cascade multipliers. In operation, the switches labeled 1 and 2 are always complementary states, and the switches labeled 7 and 8 are always complementary steps. In addition, in the first switched-state, all switches marked with "1" are opened and all switches marked with "2" are closed. In the second switched-state, all switches labeled "1" are closed and all switches labeled "2" are open. In an embodiment of the invention, the closed switches labeled 1 are capacitors C ₁ , C ₂ , C ₃ , while C ₄ , C ₅ , C ₆ discharge, and the closed switches labeled 2 have a complementary effect. In addition, the closed switches marked 7 are capacitors C ₇ , C ₈ and C ₉ , while C ₁₀ , C ₁₁ and C ₁₂ discharge, and the closed switches marked 8 have a complementary effect.

The power converter provides a 32: 1 total step-down, and the regulating circuit 16A is a buck converter with a typical 2: 1 depressurization ratio. In addition, if the input voltage is 32 V and the output voltage is 1 V, the switches of the second switching network 12D will block 2 volts while the switches in the first switching network 12A block 8 volts. will be.

Modular architectures with the basic building blocks shown in FIGS. 1-4 can also be configured to handle AC input voltages. One of the key characteristics of switched capacitor converters is their ability to operate efficiently over large input ranges by reconfiguring the switched capacitor network. If the AC barrier voltage (e.g. 60 Hz & 120 V _RMS ) is regarded as a slow flowing DC voltage, then the front-end switched capacitor stage is a relatively stable DC voltage, time-varying input voltage).

120 V _RMS superimposed on a single 60 Hz cycle with developed DC voltage A diagram of the AC waveform is as shown in FIG. The AC switching network includes other configurations (1/3, 1/2, 1/1) processed according to the inversion step. It is also designed to maintain a DC voltage below 60V. Once the AC voltage has developed, the operation of regulating circuit 16A to produce the final output voltage is as in FIG. Another switching network 16A needs to be located between the AC switching network 13A and the regulating circuit 16A for better voltage conditions. If this is the case, the AC switching network 13A is a specific purpose switching network 12A so the rules for series-connected steps apply.

radians)의 양의 구간(positive portion) 동안, 도 26에 도시한 바와 같이 7로 표시된 모든 스위치들은 닫히는 반면 8로 표시된 모든 스위치들은 개방된다. 유사하게, AC 사이클(

to

radians)의 음의 구간(neg ative portion) 동안, 도 27에 도시한 바와 같이 8로 표시된 모든 스위치들은 닫히는 반면 7로 표시된 모든 스위치들은 개방된다.FIG. 25 is a diagram illustrating an AC-DC converter corresponding to the architecture shown in FIG. 24. In an embodiment of the present invention, the AC switching network 13A is a variable-structure two-phase decompression cascade multiplayer with three separate switching ratios (1/3, 1/2, 1/1). The control circuit 16A is a synchronous buckconverter, whereas the multiplier is a synchronous AC bridge. In driving terms, the switches labeled 7 and 8 are always complementary steps. AC cycle (0 to

During the positive portion of the radians, all switches labeled 7 are closed, while all switches labeled 8 are open, as shown in FIG. Similarly, the AC cycle (

to

During the negative portion of the radians, all switches labeled 8 are closed while all switches labeled 7 are open as shown in FIG. 27.

In addition to the inverting function provided by the switches labeled 7 and 8, the switches labeled 1A-1E and the switches labeled 2A-2E provide three separate conversion ratios: 1/3, 1/2, and 1. It is optionally closed or opened as shown in Table 1 to provide).

AC switching network 13A carries digital clock signal CLK. Also, the second signal CLKB is simply a complement of CLK (e.g., high when CLK is low, low when CLK is high). It can be generated or as a non-overlapping complement as is known in the art. AC switching network 13A with switching patterns set according to the first column of Table 1 provides a ste pdown ratio of 1/3. AC switching network 13A with switching patterns set according to the second column of Table 1 provides a decompression ratio of 1/2. AC switching network 13A with switching patterns set according to the first column of Table 1 provides a decompression ratio of one.

Most power supplies with barriers meet certain power factor specifications. Power factor is a dimensionless number between 0 and 1 defined as the ratio of actual power flowing to apparent power. A common method for harmonic current control and power factor increase is to use an active power factor corrector (PFC), as shown in FIG. The power-factor correction circuit 17A causes the input current to be in phase with the line voltage and also causes reactive power consumption to zero.

29 through 36 illustrate specific embodiments of power converters according to the architecture diagrams illustrated in FIGS. 1 through 4. Since the regulating circuit and the multiple regulating circuits according to the embodiment of the present invention can limit the RMS charging current and the RMS discharge current of at least one capacitor in each switching network, these switching networks are all thermally charged switching networks. However, if there are decoupling capacitors 9A or 9B, the ability of the regulating circuit to limit the RMS charging and discharging current can be reduced. Capacitors 9A or 9B are optional and use capacitor Co to maintain a very constant output voltage. In addition, for the sake of simplicity, the switching network of each embodiment has a single conversion ratio. However, reconfigured switching networks that provide power conversion at a plurality of separate conversion ratios may be used instead.

 In driving terms, the switches labeled 1 and 2 are always complementary. Thus, in the first switching state, all switches marked as "1" are opened and all switches marked as "2" are closed. In the second switching state, all switches marked "1" are closed and all switches marked "2" are all open. Similarly, the switches labeled "3" and "4" are in a complementary state, and the switches labeled "5" and "6" are in a complementary state, and the switches labeled "7" and "8". Are in a complementary state. Typically, the regulating circuits are driven at higher switching frequencies than the switching networks. However, no switching frequencies are required between the switching networks and the regulating circuits.

FIG. 29 is a diagram of a step-up converter corresponding to the architecture shown in FIG. 1. In an embodiment of the invention, the switching network 12A is a two-phase step-up cascade multiplier with a switching ratio of 1: 3, while the regulating circuit 16A is a two-phase booster converter. phase boost converter). On the driving side, the closed switches labeled 1 and the open switches labeled 2 charge the capacitors C ₃ and C ₄ while C ₁ and C ₂ discharge. In contrast, open switches labeled ₁ and closed switches labeled ₂ charge capacitors C ₁ and C ₂ while C ₃ and C ₄ discharge.

FIG. 30 is a diagram illustrating a bidirectional step-down converter corresponding to the architecture shown in FIG. 1A. In an embodiment of the invention, the switching network 12A is a two-phase step-down cascade multiplier with a 4: 1 switching ratio, while the regulating circuit 16A is a synchronous bu converter. to be. On the driving side, the closed switches labeled 1 and the open switches labeled ₂ charge capacitors C ₁ , C ₂ and C ₃ , while capacitors C ₄ , C ₅ And C ₆ is discharged. In contrast, the open switches labeled 1 and the closed switches labeled 2 charge capacitors C ₄ , C ₅ and C ₆ , while discharging capacitors C ₁ , C ₂ and C ₃ . All of the active elements are implemented as switches, allowing the converter to handle power in both directions.

FIG. 31 is a diagram illustrating a step-up converter configuration corresponding to the architecture illustrated in FIG. 3. In an embodiment of the invention, the regulating circuit 16A is a boost converter while the switching network 12A is a two-phase step-up serie s-parallel SC converter with a 2: 1 switching ratio. . On the drive side, the closed switches labeled 1 charge capacitor C ₂ , while discharging capacitor C ₁ . Closed switches marked 2 have a complementary effect.

FIG. 32 is a diagram illustrating a bidirectional up-do wn converter corresponding to the architecture shown in FIG. 3. In an embodiment of the invention, the regulating circuit 16A is a synchronous four switch buck-boost converter, while the switching network 12A is a two-phase boost cascade multiplayer with a 4: 1 switching ratio. step-up cascade multiplier). On the driving side, the closed switches labeled 1 charge capacitors C ₄ , C ₅ and C ₆ , while discharging capacitors C ₁ , C ₂ and C ₃ . Closed switches marked 2 have a complementary effect. All of the active elements are implemented as switches, allowing the converter to handle power in both directions.

FIG. 3 is a diagram illustrating an inverting up-down converter corresponding to the architecture shown in FIG. 2. In an embodiment of the invention, the switching network 12A is a ste p-up series parallel SC converter with a 2: 1 switching ratio and the regulating circuit 16A is a buck / boost converter. The switching network 12B is a step-up series-parallel SC convertor with a 2: 1 conversion ratio. On the driving side, the closed switches labeled ₁ charge capacitor C ₁ , while the closed switches labeled 2 discharge capacitor C ₁ . Similarly, closed switches labeled 7 discharge capacitor C ₂ , while closed switches labeled 8 charge capacitor C ₂ .

FIG. 34 is a diagram illustrating a bidirectional inverting up-down conve rter corresponding to the architecture shown in FIG. 2. In an embodiment of the invention, the switching network 12A is a two-phase step-up serial-to-parallel SC converter with a 2: 1 switching ratio, while the regulating circuit 16A is a synchronous buck / boost converter and the switching network 12B is a 2: 1 switching ratio. It is a two-phase step-up series-parallel SC converter. On the driving side, the closed switches labeled ₁ charge capacitor C ₁ , while discharging capacitor C ₂ . Closed switches marked 2 have a complementary effect. Similarly, the closed switches labeled 7 charge capacitor C ₄ , while discharging capacitor C ₃ . Closed switches marked 2 have a complementary effect. All of the active elements are implemented as switches, allowing the converter to process power in both directions.

FIG. 35 is a diagram illustrating a ste p-down converter corresponding to the block diagram of FIG. 4. In an embodiment of the invention, the regulating circuit 300A is a boost converter and the switching network 200 is a two-phase step-up series-parallel SC converter with a 2: 1 switching ratio. converter, and regulating circuit 300B is a boost converter. On the drive side, the closed switches labeled 1 are capacitors C ₁ And C ₂ while charging capacitor C ₃ And C ₄ is discharged. Closed switches marked 2 have a complementary effect.

FIG. 36 is a diagram illustrating a bi directional up-down converter corresponding to the block diagram of FIG. 4. In an embodiment of the invention, the regulation circuit 300A is a synchronous boost converter.

boost converter, the switching network 200 is a two-phase fractional step-down series parallel SC converter with a 3: 2 switching ratio, and the regulating circuit 300B is a synchronous buck converter. buck converter). On the drive side, the closed switches marked 1 are capacitor C ₃ And capacitors C ₁ while charging C ₄ And C ₂ is discharged. Closed switches marked 2 have a complementary effect. All of the active elements are implemented as switches, allowing the converter to handle power in both directions.

 The topology of the regulating circuit can be any type of power converter with the ability to regulate the output voltage, synchronous buck, three-level synchronous buck, SEPIC, soft switching (so ft switched or resonant converters, but the type is not limited. Similarly, switching networks may realize various switched capacitor topologies depending on the desired voltage conversion and allowed switch voltage.

Having described one or more preferred embodiments, it will be apparent to those skilled in the art that these circuits, techniques and concepts may be used in other integrated embodiments. Accordingly, the scope of the patent is not limited to the illustrated embodiments, but may be limited only by the spirit and scope of the appended claims.

Claims (32)

In the apparatus for power conversion,
The apparatus includes a converter having an input terminal and an output terminal, the converter including an adjusting circuit, the adjusting circuit including an inductance and switching elements coupled to the inductance, the switching elements being between switching configurations. Switch control, wherein said regulating circuit maintains an average DC current through said inductance and includes a switching network having an input port and an output port, said switching network comprising charge storage elements and charge storage elements. And switching elements connected to the switching elements, wherein the switching elements perform switch control between the switch elements in one switch configuration, the switching elements forming a first array of charge storage elements, the charge storage element being the switching network. Via one of the input port and the output port of And in another configuration, the switching elements form a second array of charge storage elements, the charge storage element being discharged through one of the input port and the output port of the switching network, the switching network And at least one of the regulating circuits connected between the output terminals of the converter, wherein the switching network is a thermally charged switching network, and the regulating circuit is connected between the converter and the output terminals of the switching network. And at least one of the switching networks is a multi phase switching network, the switching network and the regulating circuit are bidirectional, the regulating circuit is multi phase, and the regulating circuit is an input terminal of the converter. Between the input port of the switching network and Wherein the switching network is a thermally charged switching network, wherein the regulating circuit is connected between the input terminal of the converter and the input port of the switching network, and at least one of the switching networks is multiphase. A switching network, said switching network and said regulating circuit are bidirectional, said regulating circuit being polyphase, said switching circuit being connected between said regulating circuit and an additional regulating circuit, said regulating circuit being said switching network and an additional switching network. The device characterized in that connected between. The method of claim 1,
The switching network comprises a reconfiguration switching network. The method according to claim 1,
And said switching network comprises a multi-phase switching network. The method of claim 1,
And said regulating circuit comprises a bidirectional regulating circuit. The method of claim 1,
And said regulating circuit comprises a multi-phase regulating circuit. 5. The method of claim 4,
And said bidirectional regulation circuit comprises a switch mode power converter. 5. The method of claim 4,
And said bidirectional regulation circuit comprises a resonant power converter. The method of claim 1,
And said regulating circuit is connected to an output of said switching network. The method of claim 1,
And said regulating circuit is connected between the output terminal of said converter and said switching network, said switching network being a thermally charged switching network. The method of claim 1,
The at least one regulating circuit is connected between an output terminal of the converter and the at least one switching network, at least one of the switching networks is a polyphase switching network, the switching network and the regulating circuit are bidirectional, And the control circuit is polyphase. The method of claim 1,
And said regulating circuit is connected between an input terminal of said converter and an input port of said switching network, said switching network being a thermally charged switching network. The method of claim 1,
The regulating circuit is connected between an input terminal of the converter and an input port of the switching network, at least one of the switching network is a polyphase switching network, the switching network and the regulating circuit are bidirectional, and the regulating circuit is Device characterized in that it is polyphase. The method of claim 1,
The switching circuit is connected between the regulating circuit and the additional regulating circuit. The method of claim 1,
The control circuit is connected between the switching network and an additional switching network. An apparatus comprising a converter having an input terminal and an output terminal, the apparatus comprising:
The converter comprises a switching network having an input port and an output port, the switching network comprising charge storage elements, the switching elements being connected to the charge storage elements, in at least one configuration, within a selected configuration. Controllable to arrange the charge storage elements, wherein the switching elements form a first group of charge storage elements to discharge the charge storage elements through an output port of the switching network, and in another configuration, the switching element Form a second group of charge storage elements to charge the charge storage elements through an input port of the switching network, the bidirectional control circuit comprising at least one of an input terminal of the converter and an input port of the switching network; Output terminal of the converter and the switch And wherein connected between the output port of the called network. 16. The method of claim 15,
And said switching network comprises a polyphase switching network. 16. The method of claim 15,
And said bidirectional regulation circuit comprises a buck / boost circuit. 16. The method of claim 15,
And said bidirectional regulation circuit comprises a divided pi circuit. In a converter having an input terminal and an output terminal,
The converter includes a switching network having an input port and an output port, the switching network comprising charge storage elements, wherein the switching elements comprise the charge storage for arranging the charge storage elements in any one of a plurality of configurations. And in one configuration, the switching elements form a first group of charge storage elements for discharging the charge storage elements through an output port of the switching network, and in another configuration, the switching The elements form a second group of charge storage elements for charging the charge storage elements via an input port of the switching network, the regulating circuit being configured to provide a stepped-up voltage, Connected between an output terminal and an output port of the switching network. Converter characterized in that. In a device having an input terminal and an output terminal,
The apparatus comprises a switching network having an input port and an output port, the switching network comprising charge storage elements, the switching elements being connected to the charge storage elements and arranged in a plurality of configurations. Controllable to switching elements, in one configuration, the switching elements form a first group of charge storage elements for discharging the charge storage elements through an output port of the switching network, and another configuration Wherein, the switching elements form a second group of charging storage elements to charge the charging storage elements through an input port of the switching network, the source control circuitry being configured to include an input terminal of the converter and an input port of the switching network. Device, characterized in that connected between. 21. The method of claim 20,
And a load regulation circuit connected between the output terminal of the converter and the output port of the switching network. Manufacturing comprising regulating circuits and multiple switching networks with inputs and outputs to allow modular interconnection for assembly of DC-DC converters. 23. The method of claim 22,
At least one switching network comprises a switched capacitor network. The method of claim 22,
The switched capacitor network comprises a switched capacitor network insulated. 25. The method of claim 24,
Wherein said thermally charged switched capacitor network comprises a cascade multiplayer. 26. The method of claim 25,
Wherein said cascade multiplayer is driven by complementary clock current sources. The method of claim 22,
At least one regulating circuit comprises a linear regulator. The method of claim 22,
Wherein said DC-DC converter comprises switched capacitor networks connected in series. The method of claim 22,
And said DC-DC converter comprises multiple regulating circuits sharing a common switching network. The method of claim 1,
And the switching network is configured as an AC switching network. 31. The method of claim 30,
And a power-factor correction circuit coupled to the AC switching network. 32. The method of claim 31,
And said power factor improving circuit is connected between said AC switching network and said regulating circuit.

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