CN121417725B - Power distribution method, device, equipment and medium of asymmetric inverter system - Google Patents
Power distribution method, device, equipment and medium of asymmetric inverter systemInfo
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Abstract
本发明公开了一种非对称逆变器系统的功率分配方法、装置、设备及介质，包括：获取非对称逆变器系统总电压调制波和权重因子，根据预设的载波调制方式；将三角载波转换为三电平逆变器使用的上载波和下载波，将三角载波转换为两电平逆变器使用的中间载波，在一个调制波周期内，在所述权重因子大于权重三角波的瞬时幅值时，根据中间载波的幅值，将两电平逆变器的电压箝位至第一最大电压调制波，根据所述总电压调制波，计算三电平逆变器的补偿电压调制波；在所述权重因子小于权重载波瞬时幅值时，将三电平逆变器的电压箝位至第二最大电压调制波，根据所述总电压调制波，计算两电平逆变器的补偿电压调制波。可以实现功率灵活分配的动态管理。
This invention discloses a power distribution method, apparatus, device, and medium for an asymmetric inverter system, comprising: acquiring the total voltage modulation wave and weighting factor of the asymmetric inverter system; according to a preset carrier modulation method; converting a triangular carrier into an upper carrier and lower carrier used by a three-level inverter, converting the triangular carrier into an intermediate carrier used by a two-level inverter; within one modulation wave cycle, when the weighting factor is greater than the instantaneous amplitude of the weighted triangular wave, clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier; calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave; when the weighting factor is less than the instantaneous amplitude of the weighted carrier, clamping the voltage of the three-level inverter to a second maximum voltage modulation wave; and calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave. This enables dynamic management of flexible power distribution.
Description
Technical Field
The present invention relates to the field of power distribution technologies, and in particular, to a power distribution method, apparatus, device, and medium for an asymmetric inverter system.
Background
An open winding permanent magnet synchronous motor (OW-PMSM) double inverter system becomes a research hot spot in the fields of new energy automobiles and the like by virtue of high voltage utilization rate, control flexibility and strong fault tolerance. The asymmetric double inverter scheme provides a good balance between cost and performance. In this system, to achieve active energy management between the two side power sources, the active power of the double inverter must be independently and flexibly controlled.
The prior art typically employs a linear strategy such as 180 deg. decoupled modulation. According to the method, the reference voltage is decomposed into independent vectors with 180-degree phase difference through mathematical decoupling, so that stable control of the system is realized, and the power of the inverters on two sides is distributed by means of fixed decoupling coefficients.
However, the above method relies on complex mathematical decoupling operation, and the decoupling coefficient is usually in a small interval, lacks flexible independent control dimension, and is difficult to realize dynamic management of flexible power distribution under complex working conditions.
Disclosure of Invention
The embodiment of the invention provides a power distribution method, a device, equipment and a storage medium of an asymmetric inverter system, which are used for solving the technical problem of dynamic management for realizing flexible power distribution of an asymmetric inverter under a complex working condition in the prior art.
In a first aspect, an embodiment of the present invention provides a power distribution method of an asymmetric inverter system, including:
Acquiring total voltage modulation waves and weight factors set by a user when an asymmetric inverter system operates, wherein the asymmetric inverter comprises a two-level inverter and a three-level inverter;
Generating a modulation triangular carrier according to a preset carrier modulation mode, and generating a weight triangular carrier according to a value range corresponding to a weight factor;
The method comprises the steps of converting a triangular carrier into an upper carrier and a lower carrier used by a three-level inverter, converting the triangular carrier into an intermediate carrier used by a two-level inverter, and providing a unified modulation reference and clamping level for the asymmetric inverter by using the upper carrier, the intermediate carrier and the lower carrier;
In a modulation wave period, when the weight factor is larger than the instantaneous amplitude of the weight triangular wave, clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier wave, and calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, wherein the first maximum voltage modulation wave is a limit value of the voltage amplitude modulated by the intermediate carrier wave;
When the weight factor is smaller than the instantaneous amplitude of the weight triangular wave, according to the amplitude of the upper carrier wave and the lower carrier wave, the voltage of the three-level inverter is clamped to a second maximum voltage modulation wave, and according to the total voltage modulation wave, the compensation voltage modulation wave of the two-level inverter is calculated, wherein the second maximum voltage modulation wave is the limit value of the voltage amplitude modulated by the upper carrier wave and the lower carrier wave.
In a second aspect, an embodiment of the present invention further provides a power distribution apparatus of an asymmetric inverter system, including:
the acquisition module is used for acquiring the total voltage modulation wave and the weight factor set by a user when the asymmetric inverter system operates, and the asymmetric inverter comprises a two-level inverter and a three-level inverter;
the generation module is used for generating a modulation triangular carrier according to a preset carrier modulation mode and generating a weight triangular carrier according to a value range corresponding to the weight factor;
The conversion module is used for converting the triangular carrier into an upper carrier and a lower carrier used by the three-level inverter, converting the triangular carrier into an intermediate carrier used by the two-level inverter, and providing a unified modulation reference and clamping level for the asymmetric inverter by utilizing the upper carrier, the intermediate carrier and the lower carrier;
The first clamping module is used for clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier wave when the weight factor is larger than the instantaneous amplitude of the weight triangular wave in one modulation wave period, and calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, wherein the first maximum voltage modulation wave is a limit value of the voltage amplitude modulated by the intermediate carrier wave;
And the second clamping module is used for clamping the voltage of the three-level inverter to a second maximum voltage modulation wave according to the amplitude of the upper carrier wave and the lower carrier wave when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave, and calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave, wherein the second maximum voltage modulation wave is a limit value of the voltage amplitude modulated by the upper carrier wave and the lower carrier wave.
In a third aspect, an embodiment of the present invention further provides an apparatus, including:
One or more processors;
storage means for storing one or more programs,
The one or more programs, when executed by the one or more processors, cause the one or more processors to implement the power distribution method of the asymmetric inverter system as provided by the above embodiments.
In a fourth aspect, embodiments of the present invention also provide a storage medium containing computer executable instructions, which when executed by a computer processor, are used to perform a power distribution method of an asymmetric inverter system as provided by the above embodiments.
The power distribution method, the device, the equipment and the storage medium of the asymmetric inverter system are characterized in that a total voltage modulation wave and a weight factor set by a user when the asymmetric inverter system operates are obtained, the asymmetric inverter comprises a two-level inverter and a three-level inverter, a modulating triangular carrier is generated according to a preset carrier modulation mode, a weight triangular carrier is generated according to a value range corresponding to the weight factor, the triangular carrier is converted into an upper carrier and a lower carrier used by the three-level inverter, the triangular carrier is converted into an intermediate carrier used by the two-level inverter, the upper carrier, the intermediate carrier and the lower carrier are utilized to provide unified modulation reference and clamping level for the asymmetric inverter, in a modulation wave period, when the weight factor is larger than the instantaneous amplitude of the weight triangular wave, the voltage of the two-level inverter is clamped to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier, the compensating voltage modulation wave of the three-level inverter is calculated according to the total voltage modulation wave, the first modulating wave is a limit value of the voltage amplitude of the intermediate carrier, and the maximum voltage modulation wave is calculated according to the amplitude of the maximum voltage amplitude of the intermediate carrier and the amplitude of the three-level inverter when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave, and the amplitude of the maximum voltage modulation wave is calculated according to the maximum amplitude of the intermediate carrier and the amplitude of the intermediate carrier. By setting different amplitude intervals for the subcarriers sharing the same phase and frequency, the two inverters have independent modulation spaces in the same modulation period, so that strong coupling caused by direct addition is avoided, the coupling degree is reduced, independent adjustment of weight is realized, further dynamic management of flexible power distribution can be realized under complex working conditions, clamping can be utilized, the switching operation frequency of one side inverter is reduced, and further the overall switching consumption of the system is reduced.
Drawings
The accompanying drawings, which are included to provide a further understanding of the invention and are incorporated in and constitute a part of this specification, illustrate embodiments of the invention and together with the description serve to explain the invention.
Fig. 1 is a flowchart of a power distribution method of an asymmetric inverter system according to a first embodiment of the present invention;
Fig. 2 is a schematic diagram of an asymmetric inverter topology in a power distribution method of an asymmetric inverter system according to a first embodiment of the present invention;
fig. 3 is a schematic diagram of modulation in a power distribution method of an asymmetric inverter system according to a first embodiment of the present invention;
FIG. 4 is a schematic diagram of a two-level inverter clamp in a power distribution method for an asymmetrical inverter system according to a first embodiment of the present invention;
Fig. 5 is a flow chart of a power distribution method of an asymmetric inverter system according to a second embodiment of the present invention;
fig. 6 is a schematic diagram of clamping when the modulation degree is smaller than the first maximum voltage modulation wave in the power distribution method of the asymmetric inverter system according to the second embodiment of the present invention;
Fig. 7 is a schematic diagram of clamping when the modulation degree is greater than the first maximum voltage modulation wave in the power distribution method of the asymmetric inverter system according to the second embodiment of the present invention;
fig. 8 is a schematic structural diagram of a power distribution apparatus of an asymmetric inverter system according to a fourth embodiment of the present invention;
Fig. 9 is a schematic structural diagram of an apparatus according to a fourth embodiment of the present invention.
Detailed Description
The invention is described in further detail below with reference to the drawings and examples. It is to be understood that the specific embodiments described herein are merely illustrative of the invention and are not limiting thereof. It should be further noted that, for convenience of description, only some, but not all of the structures related to the present invention are shown in the drawings.
Example 1
Fig. 1 is a flowchart of a power distribution method of an asymmetric inverter system according to an embodiment of the present invention, where the method may be performed by a power distribution device of the asymmetric inverter system, and specifically includes the following steps:
step 110, obtaining a total voltage modulation wave and a weight factor set by a user when an asymmetric inverter system operates, wherein the asymmetric inverter comprises a two-level inverter and a three-level inverter.
The existing open winding motor driving system mostly adopts a single direct current bus power supply topology, and zero sequence current flow of the system is easy to cause common mode interference and extra loss. In order to fundamentally eliminate the defect, two ends of the motor can be respectively connected to two sets of direct current sources which are isolated from each other at present, so that zero sequence loops do not exist between buses. The independent bus structure can be realized in the following two forms:
1. the floating capacitor is used as a dynamic reactive power source, and the terminal voltage of the floating capacitor is regulated in real time to change the inverter synthesis vector space, so that the output current waveform is optimized. However, in order to ensure stable operation of the system, continuous sampling and closed-loop control are required to be performed on the capacitor voltage, so that a control algorithm is complex and hardware sampling channels are increased;
2. The two side inverters are powered by two separate dc sources, which may be chemical batteries, fuel cells, or a combination thereof. By adopting asymmetric configuration of different level numbers or different direct current voltages, the equivalent switching frequency can be improved, the output waveform can be improved and a physical channel for energy management at two sides can be naturally formed on the premise of not obviously increasing the power device. In particular, in a dual-battery pack scene of an electric automobile, an active equalization state of charge (SoC) is required, and in a mixed scene of a fuel battery and a battery, the unidirectional output characteristic of the fuel battery and the battery charging requirement are required to be considered.
The first form requires real-time adjustment of the capacitor terminal voltage to optimize the vector space, which can lead to a dramatic increase in control algorithm complexity. Thus, the second mode is commonly employed in the prior art. An asymmetric configuration consisting of different numbers of levels or different dc voltages may be employed. In the present embodiment, an asymmetric configuration of different numbers of levels is adopted. The asymmetric topology not only improves the output waveform quality by increasing the level number, but also provides a physical basis for energy management of the two-side power supply. In particular, in an electric vehicle application where two sides are powered by independent battery packs, it is necessary to actively control the power flow to equalize the state of charge (SoC) of the battery, and in a system where the fuel cell and the battery are mixed, it is necessary to cope with the unidirectional output power characteristics of the fuel cell and to realize the charge management of the battery.
Under the power supply of double direct current sources, the key problem to be solved by the system is how to dynamically distribute active power between two independent power sources, simultaneously maintain the output voltage quality, and meet the requirements of specific working conditions, such as unidirectional output of a fuel cell and battery equalization.
In an asymmetric topology (e.g., three-level + two-level), where the output voltage is synthesized by two independent dc sources, under conventional PWM modulation, a control algorithm typically forces the switching frequencies of the two-sided inverters to remain synchronized and continuous in order to ensure sinusoidal and distortion-free output waveforms. This results in a system with a natural coupling equation that limits the number of control variables. Therefore, it is generally necessary to determine the power ratio of the two-sided inverter by a fixed decoupling coefficient k. Once set, this ratio remains unchanged during operation. Making the system lose the ability to adjust the power distribution based on real-time requirements such as battery equalization or efficiency maximization or thermal management.
In this embodiment, fig. 2 is a schematic diagram of an asymmetric inverter topology in a power distribution method of an asymmetric inverter system according to an embodiment of the present invention, and referring to fig. 2, the asymmetric inverter includes a two-level inverter and a three-level inverter.
In this embodiment, a weight factor may be set by itself according to a real-time requirement of a user, where the weight factor range (0, 1) may represent a duty ratio of an acting time of two power strategies in one modulation wave period, where each strategy represents a full load state of one of the inverters, and multiple power distribution effects may be achieved by adjusting the acting time of the two power strategies. The user can set reasonable weight factors according to actual demands.
In Pulse Width Modulation (PWM) techniques, a carrier wave is a reference signal used to compare a reference sinusoidal voltage (or space vector) to one or more periodic waveforms to produce switching pulses. The carrier stack (CARRIERLAYER) refers to a plurality of carriers used in parallel or superimposed in the same PWM sampling period, each carrier corresponding to one modulation scheme or one level. Through lamination (stacking) or phase shift (phase-shift) of different carriers, the aims of multi-level inverter, double-inverter cooperative modulation, harmonic reduction and the like can be achieved.
And 120, generating a modulated triangular carrier according to a preset carrier modulation mode, and generating a weight triangular carrier according to a value range corresponding to the weight factor.
In this embodiment, carrier stacking may be introduced into the asymmetric topology proposed herein, and two independent inverters are integrated at the control level, and the modulation degree is defined as:
Where V ref is a double inverter reference vector and V dc is a low side dc bus voltage. The M modulation is the same as the conventional SPWM modulation, except that the DC voltages on both sides are unified to an equivalent value so as to drive both inverters simultaneously under the same modulation M.
Because of the symmetry of the three phases, in one fundamental wave period, the output power of the three phases is equal, taking the phase A as an example, and the reference voltage and the current value of the phase A are defined as follows:
is the reference voltage of the phase a, The value of the current in the phase A is set to be the value of the current in the phase A,In order to achieve the degree of modulation,Is the phase angle, represents the real-time phase of the output waveform,Is the power factor angle and represents the phase difference between voltage and current.
Fig. 3 is a modulation schematic diagram of a power distribution method of an asymmetric inverter system according to an embodiment of the present invention, referring to fig. 3, which shows a dynamic distribution relationship of reference voltages of two side inverters, wherein u 3L is an a-phase three-level side reference voltage, u 2L is an a-phase two-level side reference voltage under the strategy, then
,Is the total voltage waveform that the system eventually needs to output, u 3L is the reference voltage on the three-level side, and u 2L is the reference voltage on the two-level side. The average output power of phase a over a period is expressed as:
, wherein, Representing average output power over a fundamental period
In fig. 3, three triangular carriers are shown, which are arranged in a stacked manner in the vertical direction of the [ -1,1] interval, and together construct the total modulation space of the system, an upper carrier C max and a lower carrier C min, which are respectively located in the high voltage region [1/3,1] and the low voltage region [ -1, -1/3], and are jointly responsible for modulation of the three-level inverter, wherein u 3L is compared with the upper carrier C max to obtain the switching states of the three-level sides S X11 and S x13, and u 3L is compared with the lower carrier C min to obtain the switching states of the three-level sides S X12 and S x14. The middle carrier C mid is symmetrically distributed on two sides of the zero axis, the interval is [ -1/3,1/3], and the middle carrier C mid is used for modulating a two-level inverter, wherein u 2L is compared with the middle carrier C mid to obtain the switching states of S X21 and S X22 on two-level sides. By the above relation, the triangular carrier participating in the modulation can be generated according to the improved carrier modulation mode. In addition, the received weight factors can be used to determine the value range corresponding to the weight factors, such as the range (0, 1), and the weight triangular carrier can be generated.
And 130, converting the triangular carrier into an upper carrier and a lower carrier used by the three-level inverter, converting the triangular carrier into an intermediate carrier used by the two-level inverter, and providing a unified modulation reference and clamping level for the asymmetric inverter by using the upper carrier, the intermediate carrier and the lower carrier.
The method for generating the upper carrier, the middle carrier and the lower carrier by using the triangular carrier respectively comprises the steps of linearly transforming the triangular carrier respectively to generate the upper carrier, the lower carrier and the middle carrier, wherein the amplitudes of the upper carrier, the lower carrier and the middle carrier are equal, the amplitudes of the upper carrier, the lower carrier and the middle carrier are consistent with the amplitude range of the total voltage modulation wave, the upper carrier and the lower carrier are positioned in a high voltage area and used for modulating a three-level inverter, and the middle carrier is positioned between the upper carrier and the lower carrier and used for modulating a two-level inverter. In an asymmetric double inverter, a unified modulation reference is required to ensure that the outputs of the two side inverters are added in the same fundamental wave period to obtain a target alternating voltage. To achieve the above object, it is necessary to linearly transform the triangular carrier frequency to generate three subcarriers having equal amplitude and equal phase. And the unified modulation space is formed together, and the same reference standard and the same clamping level are provided for the inverters on two sides in the same PWM period, so that the power distribution, the unified modulation depth and the waveform quality maintenance are realized.
And 140, clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier wave when the weight factor is larger than the instantaneous amplitude of the weight triangular wave in one modulation wave period, and calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, wherein the first maximum voltage modulation wave is a limit value of the amplitude of the voltage modulated by the intermediate carrier wave.
In a modulation wave period, when the weight factor is larger than the instantaneous amplitude of the weight triangular wave, the system enters a two-level inverter adjustable region. And judging whether the two-level inverter adjustable region is entered or not by utilizing the comparison relation between the weight factors and the instantaneous amplitude of the weight triangular wave. The method for clamping the voltage of the two-level inverter to the first maximum voltage modulation wave according to the amplitude of the intermediate carrier wave, and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave can comprise clamping the voltage of the two-level inverter to the first maximum voltage modulation wave corresponding to the intermediate carrier wave when the phase current is positive, calculating the voltage modulation wave of the three-level inverter according to the total voltage modulation wave, and clamping the voltage of the two-level inverter to the first maximum negative voltage modulation wave corresponding to the intermediate carrier wave when the phase current is negative, and calculating the voltage modulation wave of the three-level inverter according to the total voltage modulation wave.
After entering the adjustable region of the two-level inverter, the voltage of the two-level inverter can be clamped to a first maximum voltage modulation wave, and the voltage and the current are in the same direction by clamping to the first maximum voltage modulation wave, so that the power of the two-level inverter is at the maximum. Fig. 4 is a schematic diagram of clamping a two-level inverter in a power distribution method of an asymmetric inverter system according to a first embodiment of the present invention, referring to fig. 4, the output power of the two-level inverter is maximized, the reference voltage is clamped to 1/3 in a positive half cycle interval of cos θ >0, and the reference voltage is clamped to-1/3 in a negative half cycle interval of cos θ < 0. The 1/3 and-1/3 can be used as the first maximum voltage modulation wave. The method can calculate the power output by the two-level inverter in the adjustable region of the two-level inverter, and calculate the compensation voltage modulation wave of the three-level inverter in the adjustable region of the two-level inverter based on the clamping voltage and the total voltage modulation wave of the two-level inverter.
And 150, clamping the voltage of the three-level inverter to a second maximum voltage modulation wave according to the amplitude of the upper carrier wave and the lower carrier wave when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave, and calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave, wherein the second maximum voltage modulation wave is a limit value of the amplitude of the voltage modulated by the upper carrier wave and the lower carrier wave.
Accordingly, since the maximum value of the reference triangular carrier is 1, only when the weight factor is smaller than the instantaneous value of the weight triangular carrier, the reference voltage of the two-level inverter is already suppressed, and the three-level inverter still has a modulation room, the output of the three-level inverter needs to be clamped, and the two-level inverter needs to be compensated. The three-level inverter may hard clamp its reference voltage according to the upper limit of the magnitude of the upper/lower carrier, i.e., the second maximum voltage modulation wave. The two-level inverter completes the modulation of the residual power by compensating the voltage (total modulation wave minus the clamped three-level output). The PWM signals of the two inverters synchronously work under the same reference carrier, and the average value of the output is strictly equal to the target sine wave in each PWM period. To achieve automatic switching of power allocation. By using the time-sharing hybrid modulation mode, the problem that the power distribution ratio is usually determined by a fixed decoupling coefficient and the degree of freedom is lacking can be solved.
In the prior art, in order to ensure linearity of an output waveform, a reference voltage applied to a two-side inverter by a conventional decoupling strategy is usually a continuously-varying sinusoidal waveform, which causes that two-side power devices need to be continuously switched by high-frequency switches in a whole electrical period, especially on a three-level inverter with higher direct-current voltage as a main force of a system, and the problem of switching loss of a peak current area is particularly remarkable. With the above method, the output of the inverter on one side is constant, the switching tube does not operate for a period of time, and the modulation wave of the inverter on the other side is still a continuously variable wave. The switching loss of the inverter on the side where clamping does not occur is not increased as compared with the original continuously-varying sine wave, and the switching loss can be effectively reduced as a whole from the system.
The method comprises the steps of obtaining a total voltage modulation wave and a weight factor set by a user when an asymmetric inverter system operates, wherein the asymmetric inverter comprises a two-level inverter and a three-level inverter, generating a modulating triangular carrier according to a preset carrier modulation mode, generating a weight triangular carrier according to a value range corresponding to the weight factor, converting the triangular carrier into an upper carrier and a lower carrier used by the three-level inverter, converting the triangular carrier into an intermediate carrier used by the two-level inverter, providing a unified modulation reference and clamping level for the asymmetric inverter by using the upper carrier, the intermediate carrier and the lower carrier, clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier when the weight factor is larger than the instantaneous amplitude of the weight triangular wave in one modulation wave period, calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, wherein the first maximum voltage modulation wave is a limit value of the amplitude of the intermediate carrier modulation, and calculating a second maximum voltage modulation wave of the three-level inverter according to the amplitude of the maximum voltage modulation wave of the upper carrier and the maximum voltage modulation wave when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave. By setting different amplitude intervals for the subcarriers sharing the same phase and frequency, the two inverters have independent modulation spaces in the same modulation period, so that strong coupling caused by direct addition is avoided, the coupling degree is reduced, independent adjustment of weight is realized, further dynamic management of flexible power distribution can be realized under complex working conditions, clamping can be utilized, the switching operation frequency of one side inverter is reduced, and further the overall switching consumption of the system is reduced.
In a preferred implementation manner of this embodiment, after the step of clamping the voltage of the two-level inverter to the first maximum voltage modulation wave according to the amplitude of the intermediate carrier wave when the weight factor is greater than the weight triangular wave and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave in the one modulation wave period, the method may further include the steps of outputting the bridge arm PWM signal P when the first maximum voltage modulation wave is greater than the intermediate carrier wave, outputting the bridge arm PWM signal N when the first maximum voltage modulation wave is less than the intermediate carrier wave, outputting the bridge arm PWM signal P when the compensation voltage modulation wave of the three-level inverter is greater than the upper carrier wave, suspending outputting the bridge arm PWM signal when the compensation voltage modulation wave of the three-level inverter is greater than the lower carrier wave and less than the upper carrier wave, and outputting the bridge arm PWM signal N when the compensation voltage modulation wave of the three-level inverter is less than the lower carrier wave. Positive/negative conduction of the two-level inverter is determined by comparison of the intermediate carrier of the first maximum voltage vs, and positive conduction, pause (intermediate level) or negative conduction (P/N/pause) of the three-level inverter is determined by three-stage comparison of the upper/lower carrier of the compensation voltage vs. The system can realize dynamic distribution of power, accurate voltage clamping and seven-segment modulation in one modulation period, thereby realizing the running targets of low harmonic wave, low switching loss, high efficiency and good voltage balance.
Example two
FIG. 5 is a schematic flow chart of a power distribution method of an asymmetric inverter system according to a second embodiment of the present invention, wherein the method is based on the above embodiment, the voltages of the three-level inverter are clamped to a second maximum voltage modulation wave according to the amplitudes of the upper carrier wave and the lower carrier wave, and the compensation voltage modulation wave of the two-level inverter is calculated according to the total voltage modulation wave, concretely, the modulation degree is defined, the time intersection point of the defined modulation degree and the first maximum voltage modulation wave is t1, t2, t3 and t4 in one modulation period, the voltages of the two-level inverter are clamped to a first maximum negative voltage modulation wave when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is positive, the compensation voltage modulation wave of the three-level inverter is calculated according to the maximum voltage modulation wave of the first maximum voltage modulation wave and the phase current is negative, the compensation voltage modulation wave of the three-level inverter is calculated according to the maximum voltage modulation wave of the three-level inverter is calculated at the maximum voltage modulation wave of 1, the maximum voltage modulation wave of the three-level inverter is calculated according to the maximum voltage modulation wave of the three-level (t 2) and the total voltage modulation wave of the three-level inverter is calculated according to the maximum voltage modulation wave of the three-level of the first voltage modulation wave is negative voltage modulation wave and the maximum voltage modulation wave of the three-level inverter voltage modulation wave, and clamping the voltage of the two-level inverter to the first maximum negative voltage modulation wave in pi/2) and (3 pi/2, t 4) time, calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, and clamping the voltage of the two-level inverter to the first maximum positive voltage modulation wave in pi/2, t 2) and (t 3,3 pi/2) time when the modulation degree is larger than the first maximum voltage modulation wave, and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave.
Referring to fig. 5, the power distribution method of the asymmetric inverter system includes:
Step 210, acquiring a total voltage modulation wave and a weight factor set by a user when an asymmetric inverter system operates, wherein the asymmetric inverter comprises a two-level inverter and a three-level inverter, a modulation triangular carrier is generated according to a preset carrier modulation mode, and a weight triangular carrier is generated according to a value range corresponding to the weight factor.
Step 220, converting the triangular carrier into an upper carrier and a lower carrier used by the three-level inverter, converting the triangular carrier into an intermediate carrier used by the two-level inverter, and providing a unified modulation reference and clamping level for the asymmetric inverter by using the upper carrier, the intermediate carrier and the lower carrier.
Step 230, clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier when the weight factor is greater than the instantaneous amplitude of the weight triangular wave in one modulation wave period, and calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, wherein the first maximum voltage modulation wave is a threshold value of the amplitude of the voltage modulated by the intermediate carrier.
And step 240, when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave, defining a modulation degree in one modulation period, defining time intersection points of the modulation degree and a first maximum voltage modulation wave as t1, t2, t3 and t4, and clamping the voltage of the two-level inverter to a first maximum negative voltage modulation wave when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is positive, and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave. And when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is negative, clamping the voltage of the two-level inverter to the first maximum positive voltage modulation wave, and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave.
In this embodiment, the modulation M may describe a dimensionless parameter of a relative magnitude between the reference voltage amplitude and the dc bus voltage. Which determines the amplitude of the inverter output voltage, the power factor and the maximum output power achievable. The specific calculation mode can be calculated by the formula. And defining time intersection points of the modulation degree and the first maximum voltage modulation wave as t1, t2, t3 and t4 according to M.
Fig. 6 is a schematic diagram of clamping when the modulation degree is smaller than the first maximum voltage modulation wave in the power distribution method of the asymmetric inverter system according to the second embodiment of the present invention, referring to fig. 6, when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave, in order to maximize the output power of the three-level inverter side, the two-level side is clamped to-1/3 in the positive half cycle interval of cos θ >0, and the two-level side is clamped to 1/3 in the negative half cycle interval of cos θ < 0. And the compensation voltage modulation wave of the three-level inverter in the adjustable region of the two-level inverter can be calculated according to the clamping voltage and the total voltage modulation wave of the two-level inverter.
Step 250 of clamping the three-level inverter to the second maximum positive voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and the time (0, t 1) and the time (t 4,2 pi), calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave, clamping the three-level inverter to the second maximum negative voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and the time (t 2, t 3), calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave, clamping the voltage of the two-level inverter to the first maximum negative voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and the time (t 1, pi/2) and the time (3 pi/2, t 4), calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, and clamping the two-level inverter to the first maximum voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and the time (pi/2, t3, pi/2) and the time (t 3, pi/2).
Fig. 7 is a schematic diagram of clamping when the modulation degree is greater than the first maximum voltage modulation wave in the power distribution method of the asymmetric inverter system according to the second embodiment of the present invention. Referring to fig. 7, the three-level inverter side output power is maximized, the reference voltage is clamped to 1 in the positive half cycle intervals of (0, t 1) and (t 4,2 pi), the reference voltage is clamped to-1 in the negative half cycle intervals of (t 2, t 3), the three-level side cannot be clamped to 1 due to the limitation of the relation of the reference voltages at two sides in the intervals of (t 1, pi/2) and (3 pi/2, t 4), the two-level side output power is minimized according to the principle of total power conservation of the system, the two-level reference voltage is clamped to-1/3, and the two-level side reference voltage is clamped to 1/3 in the intervals of (pi/2, t 2) and (t 3,3 pi/2). It is possible to determine which subinterval the current falls within based on the pre-calculated t1-t4, and thus decide whether to clamp the three-level inverter or the two-level inverter, and the positive and negative polarities of the clamps. The whole period may be divided into sub-segments depending on the intersection of the modulation degree and the first maximum voltage. Different sub-segments correspond to different clamping objects (upper/lower carrier or middle carrier) and clamping polarities (positive/negative), so that the three-level inverter or the two-level inverter respectively bears main modulation tasks, and the other side provides compensation.
The embodiment clamps the voltage of the three-level inverter to a second maximum voltage modulation wave according to the amplitude of an upper carrier wave and a lower carrier wave, calculates the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave, specifically, defines a modulation degree, defines the time intersection point of the modulation degree and the first maximum voltage modulation wave as t1, t2, t3 and t4 in one modulation period, clamps the voltage of the two-level inverter to a first maximum negative voltage modulation wave when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is positive, calculates the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, clamps the voltage of the two-level inverter to the first maximum voltage modulation wave when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is negative, calculates the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave at the maximum voltage modulation wave of the two-level inverter at the time of t1, t1 and the two-level inverter at the maximum voltage modulation wave at the time of the maximum t2, and the two-level of the two-level inverter at the maximum voltage modulation wave at the maximum t1, t2 and the two-level modulation wave at the maximum voltage modulation wave at the maximum voltage modulation wave of 2 and at the maximum 2, and clamping the voltage of the two-level inverter to the first maximum positive voltage modulation wave when the modulation degree is larger than the first maximum voltage modulation wave and the time is (pi/2, t 2) and (t 3,3 pi/2), and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave. The power distribution method can realize flexible distribution of power, elimination of modulation errors and suppression of harmonic waves in the whole modulation period, and can keep stable and reliable operation under different loads, different current directions of phases and different modulation intervals.
In another preferred implementation manner of this embodiment, after the step of clamping the voltage of the three-level inverter to the second maximum voltage modulation wave according to the magnitudes of the upper carrier wave and the lower carrier wave when the weight factor is smaller than the weight triangular wave and calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave in the one modulation wave period, the method may further include the steps of outputting the bridge arm PWM signal P when the second maximum voltage modulation wave is larger than the upper carrier wave, outputting the bridge arm PWM signal O when the second maximum voltage modulation wave is larger than the lower carrier wave and smaller than the upper carrier wave, outputting the bridge arm PWM signal N when the second maximum voltage modulation wave is smaller than the lower carrier wave, outputting the bridge arm PWM signal P when the compensation voltage modulation wave of the two-level inverter is larger than the middle carrier wave, and outputting the bridge arm PWM signal N when the compensation voltage modulation wave of the two-level inverter is smaller than the middle carrier wave. Seven-segment modulation can be adopted to provide finer voltage dispersion, the quality of an output waveform is improved, the switching times can be obviously reduced, the switching loss is reduced, the higher harmonic is suppressed, the phase synchronization of two inverters is ensured, the control logic is only amplitude comparison, and the method is easy to realize and reliable, so that an asymmetric two-level/three-level inverter can safely and economically operate in a wider working range.
Example III
Fig. 8 is a schematic structural diagram of a power distribution apparatus of an asymmetric inverter system according to a fourth embodiment of the present invention, referring to fig. 8, the power distribution apparatus of an asymmetric inverter system includes:
An acquisition module 310, configured to acquire a total voltage modulation wave and a weight factor set by a user when the asymmetric inverter system operates, where the asymmetric inverter includes a two-level inverter and a three-level inverter;
The generating module 320 is configured to generate a modulated triangular carrier according to a preset carrier modulation mode, and generate a weighted triangular carrier according to a value range corresponding to the weight factor;
The conversion module 330 is configured to convert a triangular carrier into an upper carrier and a lower carrier used by a three-level inverter, convert the triangular carrier into an intermediate carrier used by a two-level inverter, and provide a unified modulation reference and clamping level for the asymmetric inverter by using the upper carrier, the intermediate carrier and the lower carrier;
The first clamping module 340 is configured to clamp the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier when the weight factor is greater than the instantaneous amplitude of the weighted triangular wave in one modulation wave period, and calculate a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, where the first maximum voltage modulation wave is a limit value of the voltage amplitude modulated by the intermediate carrier;
And the second clamping module 350 is configured to clamp the voltage of the three-level inverter to a second maximum voltage modulation wave according to the magnitudes of the upper carrier wave and the lower carrier wave when the weight factor is smaller than the instantaneous magnitude of the weight triangular wave, and calculate a compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave, where the second maximum voltage modulation wave is a threshold value of the magnitudes of the voltages modulated by the upper carrier wave and the lower carrier wave.
The method comprises the steps of obtaining a total voltage modulation wave and a weight factor set by a user when an asymmetric inverter system operates, wherein the asymmetric inverter comprises a two-level inverter and a three-level inverter, generating a modulating triangular carrier according to a preset carrier modulation mode, generating a weight triangular carrier according to a value range corresponding to the weight factor, converting the triangular carrier into an upper carrier and a lower carrier used by the three-level inverter, converting the triangular carrier into an intermediate carrier used by the two-level inverter, providing a unified modulation reference and clamping level for the asymmetric inverter by using the upper carrier, the intermediate carrier and the lower carrier, clamping the voltage of the two-level inverter to a first maximum voltage modulation wave according to the amplitude of the intermediate carrier when the weight factor is larger than the instantaneous amplitude of the weight triangular wave in one modulation wave period, calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave, wherein the first maximum voltage modulation wave is a limit value of the amplitude of the intermediate carrier modulation, and calculating a second maximum voltage modulation wave of the three-level inverter according to the amplitude of the maximum voltage modulation wave of the upper carrier and the maximum voltage modulation wave when the weight factor is smaller than the instantaneous amplitude of the weight triangular wave. By setting different amplitude intervals for the subcarriers sharing the same phase and frequency, the two inverters have independent modulation spaces in the same modulation period, so that strong coupling caused by direct addition is avoided, the coupling degree is reduced, independent adjustment of weight is realized, further dynamic management of flexible power distribution can be realized under complex working conditions, clamping can be utilized, the switching operation frequency of one side inverter is reduced, and further the overall switching consumption of the system is reduced.
On the basis of the above embodiment, the conversion module includes:
The device comprises a conversion unit, a high-voltage area, a three-level inverter and a two-level inverter, wherein the conversion unit is used for respectively carrying out linear conversion on triangular carriers to generate an upper carrier, a lower carrier and an intermediate carrier, the amplitudes of the upper carrier, the lower carrier and the intermediate carrier are equal, the amplitudes of the upper carrier, the lower carrier and the intermediate carrier are consistent with the amplitude range of the total voltage modulation wave, the upper carrier and the lower carrier are positioned in the high-voltage area and used for modulating the three-level inverter, and the intermediate carrier is positioned between the upper carrier and the lower carrier and used for modulating the two-level inverter.
On the basis of the foregoing embodiment, the first clamping module includes:
The first clamping unit is used for clamping the voltage of the two-level inverter to a first maximum positive voltage modulation wave corresponding to the intermediate carrier when the phase current is positive, and calculating the voltage modulation wave of the three-level inverter according to the total voltage modulation wave;
and the second clamping unit is used for clamping the voltage of the two-level inverter to the first maximum negative voltage modulation wave corresponding to the intermediate carrier when the phase current is negative, and calculating the voltage modulation wave of the three-level inverter according to the total voltage modulation wave.
On the basis of the above embodiment, the second clamping module includes:
A defining unit, configured to define a modulation degree in one modulation period, and define time intersections of the modulation degree and the first maximum voltage modulation wave as t 1、t2、t3 and t 4;
A first calculation unit, configured to clamp the voltage of the two-level inverter to a first maximum negative voltage modulation wave when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is positive, and calculate a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave;
A second calculation unit for clamping the voltage of the two-level inverter to the first maximum positive voltage modulation wave when the modulation degree is smaller than the first maximum voltage modulation wave and the phase current is negative, and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave;
A third calculation unit for clamping the three-level inverter to the second maximum positive voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and within (0, t 1) and (t 4, 2pi) times, and calculating the compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave;
A fourth calculation unit for clamping the three-level inverter to a second maximum negative voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and within (t 2,t3) time, and calculating a compensation voltage modulation wave of the two-level inverter according to the total voltage modulation wave;
A fifth calculation unit for clamping the voltage of the two-level inverter to a first maximum negative voltage modulation wave when the modulation degree is greater than a first maximum voltage modulation wave and within (t 1, pi/2) and (3 pi/2, t 4) times, and calculating a compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave;
A sixth calculation unit for clamping the voltage of the two-level inverter to the first maximum positive voltage modulation wave when the modulation degree is greater than the first maximum voltage modulation wave and within (pi/2, t 2) and (t 3, 3 pi/2) times, and calculating the compensation voltage modulation wave of the three-level inverter according to the total voltage modulation wave.
On the basis of the above embodiment, the apparatus further includes:
The first signal output unit is used for outputting a bridge arm PWM signal P when the first maximum voltage modulation wave is larger than the intermediate carrier wave;
the second signal output unit is used for outputting a bridge arm PWM signal N when the first maximum voltage modulation wave is smaller than the intermediate carrier wave;
The third signal output unit is used for outputting a bridge arm PWM signal P when the compensation voltage modulation wave of the three-level inverter is larger than the upper carrier wave;
the fourth signal output unit is used for suspending outputting bridge arm PWM signals when the compensation voltage modulation wave of the three-level inverter is larger than the lower carrier wave and smaller than the upper carrier wave;
And the fifth signal output unit is used for outputting a bridge arm PWM signal N when the compensation voltage modulation wave of the three-level inverter is smaller than the lower carrier wave.
On the basis of the above embodiment, the apparatus further includes:
The sixth signal output unit is configured to output a bridge arm PWM signal P when the second maximum voltage modulation wave is greater than the upper carrier wave;
a seventh signal output unit, configured to output a bridge arm PWM signal O when the second maximum voltage modulation wave is greater than the lower carrier wave and less than the upper carrier wave;
An eighth signal output unit, configured to output a bridge arm PWM signal N when the second maximum voltage modulation wave is smaller than a lower carrier wave;
a ninth signal output unit, configured to output a bridge arm PWM signal P when the compensation voltage modulation wave of the two-level inverter is greater than the intermediate carrier;
and the tenth signal output unit is used for outputting a bridge arm PWM signal N when the compensation voltage modulation wave of the two-level inverter is smaller than the intermediate carrier wave.
The power distribution device of the asymmetric inverter system provided by the embodiment of the invention can execute the power distribution method of the asymmetric inverter system provided by any embodiment of the invention, and has the corresponding functional modules and beneficial effects of the execution method.
Example IV
Fig. 9 is a schematic structural diagram of an apparatus according to a fourth embodiment of the present invention. Fig. 9 shows a block diagram of an exemplary device 12 suitable for use in implementing embodiments of the present invention. The device 12 shown in fig. 9 is merely an example and should not be construed as limiting the functionality and scope of use of embodiments of the present invention.
As shown in fig. 9, device 12 is in the form of a general purpose computing device. The components of device 12 may include, but are not limited to, one or more processors or processing units 16, a system memory 28, and a bus 18 that connects the various system components, including system memory 28 and processing units 16.
Bus 18 represents one or more of several types of bus structures, including a memory bus or memory controller, a peripheral bus, an accelerated graphics port, a processor, and a local bus using any of a variety of bus architectures. By way of example, and not limitation, such architectures include Industry Standard Architecture (ISA) bus, micro channel architecture (MAC) bus, enhanced ISA bus, video Electronics Standards Association (VESA) local bus, and Peripheral Component Interconnect (PCI) bus.
Device 12 typically includes a variety of computer system readable media. Such media can be any available media that is accessible by device 12 and includes both volatile and nonvolatile media, removable and non-removable media.
The system memory 28 may include computer system readable media in the form of volatile memory, such as RAM30 and/or cache 32. Device 12 may further include other removable/non-removable, volatile/nonvolatile computer system storage media. By way of example only, storage system 34 may be used to read from or write to non-removable, nonvolatile magnetic media (not shown in FIG. 9, commonly referred to as a "hard disk drive"). Although not shown in fig. 9, a magnetic disk drive for reading from and writing to a removable non-volatile magnetic disk (e.g., a "floppy disk"), and an optical disk drive for reading from or writing to a removable non-volatile optical disk (e.g., a CD-ROM, DVD-ROM, or other optical media) may be provided. In such cases, each drive may be coupled to bus 18 through one or more data medium interfaces. The system memory 28 may include at least one program product having a set (e.g., at least one) of program modules configured to carry out the functions of the embodiments of the invention.
A program/utility 40 having a set (at least one) of program modules 42 may be stored in, for example, system memory 28, such program modules 42 including, but not limited to, an operating system, one or more application programs, other program modules, and program data, each or some combination of which may include an implementation of a network environment. Program modules 42 generally perform the functions and/or methods of the embodiments described herein.
Device 12 may also communicate with one or more external devices 14 (e.g., keyboard, pointing device, display 24, etc.), one or more devices that enable a user to interact with device 12, and/or any devices (e.g., network card, modem, etc.) that enable device 12 to communicate with one or more other computing devices. Such communication may occur through the I/O interface 22. Also, device 12 may communicate with one or more networks such as a Local Area Network (LAN), a Wide Area Network (WAN) and/or a public network, such as the Internet, via network adapter 20. As shown, network adapter 20 communicates with other modules of device 12 over bus 18. It should be appreciated that although not shown, other hardware and/or software modules may be used in connection with device 12, including, but not limited to, microcode, device drivers, redundant processing units, external disk drive arrays, RAID systems, tape drives, data backup storage systems, and the like.
The processing unit 16 executes various functional applications and data processing by running programs stored in the system memory 28, for example, implementing a power distribution method of an asymmetric inverter system provided by an embodiment of the present invention
Example five
A fifth embodiment of the present invention also provides a storage medium containing computer-executable instructions, which when executed by a computer processor, are configured to perform a power distribution method of an asymmetric inverter system as any one of the above embodiments provides.
The computer storage media of embodiments of the invention may take the form of any combination of one or more computer-readable media. The computer readable medium may be a computer readable signal medium or a computer readable storage medium. The computer readable storage medium can be, for example, but not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, or device, or a combination of any of the foregoing. More specific examples (a non-exhaustive list) of the computer-readable storage medium include an electrical connection having one or more wires, a portable computer diskette, a hard disk, a Random Access Memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or flash memory), an optical fiber, a portable compact disc read-only memory (CD-ROM), an optical storage device, a magnetic storage device, or any suitable combination of the foregoing. In this document, a computer readable storage medium may be any tangible medium that can contain, or store a program for use by or in connection with an instruction execution system, apparatus, or device.
The computer readable signal medium may include a propagated data signal with computer readable program code embodied therein, either in baseband or as part of a carrier wave. Such a propagated data signal may take any of a variety of forms, including, but not limited to, electro-magnetic, optical, or any suitable combination of the foregoing. A computer readable signal medium may also be any computer readable medium that is not a computer readable storage medium and that can communicate, propagate, or transport a program for use by or in connection with an instruction execution system, apparatus, or device.
Program code embodied on a computer readable medium may be transmitted using any appropriate medium, including but not limited to wireless, wireline, optical fiber cable, RF, etc., or any suitable combination of the foregoing.
Computer program code for carrying out operations of the present invention may be written in any combination of one or more programming languages, including an object oriented programming language such as Java, smalltalk, C ++ and conventional procedural programming languages, such as the "C" programming language or similar programming languages. The program code may execute entirely on the user's computer, partly on the user's computer, as a stand-alone software package, partly on the user's computer and partly on a remote computer or entirely on the remote computer or device. In the case of a remote computer, the remote computer may be connected to the user's computer through any kind of network, including a Local Area Network (LAN) or a Wide Area Network (WAN), or may be connected to an external computer (for example, through the Internet using an Internet service provider).
Note that the above is only a preferred embodiment of the present invention and the technical principle applied. It will be understood by those skilled in the art that the present invention is not limited to the particular embodiments described herein, but is capable of various obvious changes, rearrangements and substitutions as will now become apparent to those skilled in the art without departing from the scope of the invention. Therefore, while the invention has been described in connection with the above embodiments, the invention is not limited to the embodiments, but may be embodied in many other equivalent forms without departing from the spirit or scope of the invention, which is set forth in the following claims.
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| CN119577553A (en) * | 2024-12-13 | 2025-03-07 | 天津工业大学 | Fault diagnosis method for open-winding dual three-level inverter based on common-mode voltage difference |
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