CN108475837A - Device and method for generating electromagnetic waves on a transmission medium - Google Patents

Abstract

Aspects of the subject disclosure can include: receiving a plurality of communication signals; and generating a signal based on the plurality of communication signals that induces a plurality of electromagnetic waves that are at least partially confined to an outer surface of the transmission medium. Other embodiments are disclosed.

Description

Device and method for generating electromagnetic waves on a transmission medium

Cross References to Related Applications

This application is submitted by Henry et al. on October 14, 2016, and the name is "Apparatus and Methods for Generating Non-Interfering Electromagnetic Waves on an Insulated Conductor (for generating non-interfering electromagnetic wave devices and methods on insulated conductors)" in the United States Continuation-in-part and claiming priority of U.S. Application No. 15/293,929, filed October 14, 2016 by Henry et al., entitled "Apparatus and Methods for Generating Non-Interfering Electromagnetic Waves on an Uninsulated Conductor (Apparatus and method for generating non-interfering electromagnetic waves on an uninsulated conductor)" is a continuation-in-part and claims priority of U.S. Application No. 15/293,819 by Henry et al. U.S. Application No. 15/, entitled "Apparatus and Methods for Generating an Electromagnetic Wave having a Wave Mode that Mitigates Interference" filed on October 14, 2016 293,608, a continuation-in-part of, and claiming priority from, U.S. Application No. 15/293,608, filed September 23, 2016 by Henry et al., entitled "Apparatus and Methods for Sending or Receiving Electromagnetic Signals Apparatus and Methods for Electromagnetic Signals)" is a continuation-in-part and claims priority of U.S. Application No. 15/274,987, filed December 10, 2015 by Henry et al., entitled " Method and Apparatus for Coupling an Antenna to a Device" is a continuation-in-part and claims priority of U.S. Application No. 14/965,523, issued by Submitted on 16 October 2015 by Adriazola et al. entitled "Method and Apparatus for Coupling an Ante nna to a Device (Method and Apparatus for Coupling Antenna to a Device)" is a continuation-in-part of US Application No. 14/885,463 and claims priority therefrom. All portions of the aforementioned application(s) are hereby incorporated by reference in their entirety. All parts of U.S. Application Serial No. 14/799,272, filed July 14, 2015, entitled "Apparatus and Methods for Transmitting Wireless Signals," by Henry et al. here.

technical field

The subject disclosure relates to apparatus and methods for generating electromagnetic waves over a transmission medium.

Background technique

As smartphones and other portable devices become increasingly ubiquitous and data usage increases, macrocell base station equipment and existing wireless infrastructure in turn require higher bandwidth capabilities in order to address the increased demand. To provide additional mobile bandwidth, small cell deployments are being sought, where micro and pico cells provide coverage over a much smaller area than traditional macro cells.

Additionally, most homes and businesses have grown to rely on broadband data access for services such as voice, video, and Internet browsing. Broadband access networks include satellite networks, 4G or 5G wireless networks, power line communication networks, fiber optic networks, cable networks, and telephone networks.

Description of drawings

Reference will now be made to the drawings, which are not necessarily to scale, and in which:

Figure 1 is a block diagram illustrating an example non-limiting embodiment of a guided wave communication system in accordance with various aspects described herein.

Figure 2 is a block diagram illustrating an example non-limiting embodiment of a transmission device according to various aspects described herein.

3 is a graphical diagram illustrating an example non-limiting embodiment of an electromagnetic field distribution according to various aspects described herein.

4 is a graphical diagram illustrating an example non-limiting embodiment of an electromagnetic field distribution according to various aspects described herein.

5A is a graphical diagram illustrating an example non-limiting embodiment of a frequency response according to various aspects described herein.

5B is a graphical diagram illustrating an example non-limiting embodiment of a longitudinal cross-section of an insulated wire depicting a guided electromagnetic wave field at various operating frequencies in accordance with various aspects described herein.

6 is a graphical diagram illustrating an example non-limiting embodiment of an electromagnetic field distribution according to various aspects described herein.

7 is a block diagram illustrating an example non-limiting embodiment of an arc coupler in accordance with various aspects described herein.

8 is a block diagram illustrating an example non-limiting embodiment of an arc coupler in accordance with various aspects described herein.

9A is a block diagram illustrating an example non-limiting embodiment of a stub coupler in accordance with various aspects described herein.

9B is a diagram illustrating an example non-limiting embodiment of an electromagnetic distribution according to various aspects described herein.

10A and 10B are block diagrams illustrating example non-limiting embodiments of couplers and transceivers according to various aspects described herein.

11 is a block diagram illustrating an example non-limiting embodiment of a dual stub coupler in accordance with various aspects described herein.

Figure 12 is a block diagram illustrating an example non-limiting embodiment of a repeater system according to various aspects described herein.

13 illustrates a block diagram illustrating an example non-limiting embodiment of a two-way repeater in accordance with various aspects described herein.

14 is a block diagram illustrating an example non-limiting embodiment of a waveguide system according to various aspects described herein.

15 is a block diagram illustrating an example non-limiting embodiment of a guided wave communication system according to various aspects described herein.

16A and 16B are block diagrams illustrating example non-limiting embodiments of a system for managing a grid communication system according to various aspects described herein.

Figure 17A illustrates a flowchart of an example non-limiting embodiment of a method for detecting and mitigating disturbances occurring in the communication network of the systems of Figures 16A and 16B.

Figure 17B illustrates a flowchart of an example non-limiting embodiment of a method for detecting and mitigating disturbances occurring in the communication network of the system of Figures 16A and 16B.

18A, 18B and 18C are block diagrams illustrating example non-limiting embodiments of transmission media for propagating guided electromagnetic waves.

18D is a block diagram illustrating an example non-limiting embodiment of bundled transmission media according to various aspects described herein.

18E is a block diagram illustrating an example non-limiting embodiment of a graph depicting crosstalk between a first transmission medium and a second transmission medium in the bundled transmission media of FIG. 18D in accordance with various aspects described herein.

18F is a block diagram illustrating an example non-limiting embodiment of bundled transmission media for crosstalk mitigation in accordance with various aspects described herein.

18G and 18H are block diagrams illustrating example non-limiting embodiments of transmission media with inner waveguides according to various aspects described herein.

18I and 18J are block diagrams illustrating example non-limiting embodiments of connector configurations that may be used with the transmission media of FIGS. 18A, 18B, or 18C.

Figure 18K is a block diagram illustrating an example non-limiting embodiment of a transmission medium for propagating guided electromagnetic waves.

18L is a block diagram illustrating an example non-limiting embodiment of bundled transmission media for crosstalk mitigation in accordance with various aspects described herein.

18M is a block diagram illustrating an example non-limiting embodiment of exposed stubs from bundled transmission media used as antennas in accordance with various aspects described herein.

18N, 18O, 18P, 18Q, 18R, 18S, 18T, 18U, 18V, and 18W are diagrams illustrating waveguide devices for transmitting and receiving electromagnetic waves according to various aspects described herein. Block diagram of an exemplary non-limiting embodiment.

19A and 19B are block diagrams illustrating example non-limiting embodiments of dielectric antennas and corresponding gain and field strength graphs in accordance with various aspects described herein.

19C and 19D are block diagrams illustrating example non-limiting embodiments of a dielectric antenna coupled to a lens and corresponding gain and field strength graphs according to various aspects described herein.

19E and 19F are block diagrams illustrating example non-limiting embodiments of a dielectric antenna coupled to a lens with ridges and corresponding gain and field strength graphs according to various aspects described herein.

Figure 19G is a block diagram illustrating an example non-limiting embodiment of a dielectric antenna having an elliptical structure according to various aspects described herein.

19H is a block diagram illustrating an example non-limiting embodiment of near-field and far-field signals transmitted by the dielectric antenna of FIG. 19G in accordance with various aspects described herein.

191 is a block diagram of an example, non-limiting embodiment of a dielectric antenna for conditioning far-field wireless signals according to various aspects described herein.

19J and 19K are block diagrams of example non-limiting embodiments of flanges that may be coupled to dielectric antennas in accordance with various aspects described herein.

19L is a block diagram of an example non-limiting embodiment of a flange, waveguide, and dielectric antenna assembly according to various aspects described herein.

19M is a block diagram of an example non-limiting embodiment of a dielectric antenna coupled to a gimbal for directing wireless signals generated by the dielectric antenna in accordance with various aspects described herein.

Figure 19N is a block diagram of an example non-limiting embodiment of a dielectric antenna according to various aspects described herein.

19O is a block diagram of an example, non-limiting embodiment of a dielectric antenna array configurable for steering wireless signals according to various aspects described herein.

19P1, 19P2, 19P3, 19P4, 19P5, 19P6, 19P7, and 19P8 are side block diagrams of exemplary non-limiting embodiments of cables, flanges, and dielectric antenna assemblies according to various aspects described herein .

19Q1 , 19Q2 and 19Q3 are front block diagrams illustrating example non-limiting embodiments of dielectric antennas according to various aspects described herein.

20A and 20B are block diagrams illustrating example non-limiting embodiments of transmission media of FIG. 18A for inducing guided electromagnetic waves on power lines supported by utility poles.

Figure 20C is a block diagram of an example non-limiting embodiment of a communication network in accordance with various aspects described herein.

Figure 20D is a block diagram of an example non-limiting embodiment of an antenna mount for use in a communication network according to various aspects described herein.

20E is a block diagram of an example non-limiting embodiment of an antenna mount for use in a communication network according to various aspects described herein.

20F is a block diagram of an example non-limiting embodiment of an antenna mount for use in a communication network according to various aspects described herein.

Figure 21A illustrates a flowchart of an example non-limiting embodiment of a method for transmitting downlink signals.

Figure 21B illustrates a flowchart of an example non-limiting embodiment of a method for transmitting uplink signals.

Figure 21C illustrates a flowchart of an example non-limiting embodiment of a method for inducing and receiving electromagnetic waves on a transmission medium.

Figure 21D illustrates a flowchart of an example non-limiting embodiment of a method for inducing and receiving electromagnetic waves on a transmission medium.

Figure 21E illustrates a flowchart of an example non-limiting embodiment of a method for transmitting wireless signals from a dielectric antenna.

Figure 2 IF illustrates a flowchart of an example non-limiting embodiment of a method for receiving wireless signals at a dielectric antenna.

Figure 21G illustrates a flowchart of an example non-limiting embodiment of a method for detecting and mitigating disturbances occurring in a communication network.

21H is a block diagram illustrating an example non-limiting embodiment of field alignment of electromagnetic waves for mitigating propagation loss due to water accumulation on a transmission medium in accordance with various aspects described herein.

21I and 21J are block diagrams illustrating example non-limiting embodiments of electric field strengths of different electromagnetic waves propagating in the cable illustrated in FIG. 20H according to various aspects described herein.

Figure 21K is a block diagram illustrating an example non-limiting embodiment of an electric field of a Goubau wave according to various aspects described herein.

21L is a block diagram illustrating an example non-limiting embodiment of an electric field of a mixing wave according to various aspects described herein.

21M is a block diagram illustrating an example non-limiting embodiment of the electric field characteristics of a hybrid wave versus a Goubau wave according to various aspects described herein.

21N is a block diagram illustrating an example non-limiting embodiment of the mode size of a hybrid wave at various operating frequencies according to various aspects described herein.

22A and 22B are block diagrams illustrating example non-limiting embodiments of waveguide devices for transmitting hybrid waves according to various aspects described herein.

23 is a block diagram illustrating an example non-limiting embodiment of a hybrid wave emitted by the waveguide device of FIGS. 21A and 21B in accordance with various aspects described herein.

Figure 24 illustrates a flowchart of an example non-limiting embodiment of a method for managing electromagnetic waves.

25A, 25B, 25C and 25D are block diagrams illustrating example non-limiting embodiments of waveguide devices according to various aspects described herein.

25E, 25F, 25G, 25H, 25I, 25J, 25K, 25L, 25M, 25N, 25O, 25P, 25Q, 25R, 25S, and 25T are diagrams A block diagram illustrating an example non-limiting embodiment of a wave pattern and electric field profile according to various aspects described herein.

Figure 25U is a block diagram illustrating an example non-limiting embodiment of a waveguide device according to various aspects described herein.

25V, 25W, 25X are block diagrams illustrating example non-limiting embodiments of wave patterns and electric field profiles according to various aspects described herein.

Figure 25Y illustrates a flowchart of an example non-limiting embodiment of a method for managing electromagnetic waves.

Figure 25Z is a block diagram illustrating an example non-limiting embodiment of substantially orthogonal wave modes according to various aspects described herein.

25AA is a block diagram illustrating an example non-limiting embodiment of an insulated conductor according to various aspects described herein.

25AB is a block diagram illustrating an example non-limiting embodiment of an uninsulated conductor according to various aspects described herein.

25AC is a block diagram illustrating an example non-limiting embodiment of an oxide layer formed on the uninsulated conductor of FIG. 25AB according to various aspects described herein.

25AD are block diagrams illustrating example non-limiting embodiments of spectral graphs according to various aspects described herein.

25AE are block diagrams illustrating example non-limiting embodiments of spectral graphs according to various aspects described herein.

Figure 25AF is a block diagram illustrating an example non-limiting embodiment of a wave mode and electric field profile according to various aspects described herein.

25AG is a block diagram illustrating an example non-limiting embodiment for transmitting an orthogonal wave pattern according to the method of FIG. 25Y in accordance with various aspects described herein.

25AH is a block diagram illustrating an example non-limiting embodiment for transmitting an orthogonal wave pattern according to the method of FIG. 25Y according to various aspects described herein.

Figure 25AI is a block diagram illustrating an example non-limiting embodiment for selectively receiving wave patterns according to the method of Figure 25Y according to various aspects described herein.

25AJ is a block diagram illustrating an example non-limiting embodiment for selectively receiving wave patterns according to the method of FIG. 25Y according to various aspects described herein.

25AK is a block diagram illustrating an example non-limiting embodiment for selectively receiving wave patterns according to the method of FIG. 25Y according to various aspects described herein.

Figure 25AL is a block diagram illustrating an example non-limiting embodiment for selectively receiving wave patterns according to the method of Figure 25Y according to various aspects described herein.

26 is a block diagram of an example, non-limiting embodiment of a computing environment in accordance with various aspects described herein.

Figure 27 is a block diagram of an example non-limiting embodiment of a mobile network platform in accordance with various aspects described herein.

Figure 28 is a block diagram of an example non-limiting embodiment of a communication device in accordance with various aspects described herein.

Detailed ways

One or more embodiments are now described with reference to the drawings, wherein like numerals are used to refer to like elements throughout. In the following description, for purposes of explanation, numerous details are set forth in order to provide a thorough understanding of various embodiments. It is evident, however, that the various embodiments may be practiced without these details (and without application to any particular networking environment or standard).

In an embodiment, a guided wave communication system for sending and receiving communication signals such as data or other signaling via guided electromagnetic waves is presented. The guided electromagnetic waves include, for example, surface waves or other electromagnetic waves that are confined to or guided by a transmission medium. It will be appreciated that various transmission media may be used with guided wave communications without departing from the example embodiments. Examples of such transmission media may include one or more of the following (alone or in combination of one or more): wire (insulated or uninsulated, and single or multi-stranded) ; conductors of other shapes or configurations, including wire bundles, cables, rods, rails, pipes; non-conductors, such as dielectric pipes, rods, rails, or other dielectric members; combinations of conductors and dielectric materials; or other guided wave transmission media.

The induction of a guided electromagnetic wave on a transmission medium may be independent of any potential, charge or current injected or otherwise transmitted through the transmission medium as part of the circuit. For example, where the transmission medium is a wire, it should be recognized that while a small current in the wire can form in response to the propagation of a guided wave along the wire, this can be due to the propagation of an electromagnetic wave along the surface of the wire and is not a response to Formed by the potential, charge, or current injected into a wire that is part of an electrical circuit. Therefore, an electromagnetic wave traveling on a wire does not require a circuit to propagate along the surface of the wire. Therefore, the wire is a single-conductor transmission line, not part of a circuit. Also, in some embodiments, wires are not necessary, and electromagnetic waves can propagate along a single-line transmission medium that is not a wire.

More generally, a "guided electromagnetic wave" or "guided wave" as described in the subject disclosure is subjected to a physical object that is at least a portion of the transmission medium (e.g., a bare wire or other conductor, dielectric, insulated wire, conduit, or other hollow components, insulated wire bundles coated, covered or surrounded by dielectric or insulator or other wire bundles, or another form of solid or other non-liquid or non-gas transmission medium) so as to limit at least in part to The physical object is or is guided by the physical object and so as to propagate along the transport path of the physical object. Such physical objects may operate as at least a portion of a transmission medium passing through an interface of the transmission medium (e.g., an outer surface, an inner surface, an interior portion between an outer surface and an inner surface, or an interface between elements of the transmission medium). Other boundaries) guide the propagation of electromagnetic waves "guided electromagnetic waves" which in turn may carry energy and/or other data along a transmission path from a sending device to a receiving device.

Unlike free-space propagation of wireless signals, such as unguided (or unbounded) electromagnetic waves, whose strength decreases inversely with the square of the distance traveled by the unguided electromagnetic wave, guided electromagnetic waves can propagate along a transmission medium with a ratio The small amount of loss per unit distance experienced by unguided electromagnetic waves.

The circuitry allows electrical signals to propagate from the sending device to the receiving device via forward and return electrical paths, respectively. These electrical forward and return paths may be implemented by two conductors, such as two wires or a single wire and a common ground acting as the second conductor. Specifically, the current (direct and/or alternating current) from the transmitting device flows through the electrical forward path and returns as the opposite current to the transmitting source via the electrical return path. More specifically, electrons flowing in one conductor away from the sending device flow back to the receiving device via a second conductor or in the opposite direction. Unlike electrical signals, guided electromagnetic waves can propagate along a transmission medium (e.g., bare conductors, insulated conductors, conduits, nonconductive materials such as dielectric strips, or any other type of object suitable for propagating surface waves) from a sending device to a receiving device. device, or vice versa, without the need for the transmission medium to be part of the circuit between the sending device and the receiving device (ie, without an electrical return path). Although electromagnetic waves can propagate in open circuits, that is, circuits that have no electrical return path or have breaks or voids that prevent current from flowing through the circuit, it should be noted that electromagnetic waves can also travel along the surface of a transmission medium that is actually part of the circuit. spread. That is, electromagnetic waves may travel along a first surface of the transmission medium having a forward electrical path and/or along a second surface of the transmission medium having an electrical return path. Thus, guided electromagnetic waves can propagate along the surface of a transmission medium from a sending device to a receiving device, or vice versa, with or without an electrical circuit.

For example, this allows guided electromagnetic waves to be transmitted along a transmission medium (eg, a dielectric strip) that has no conductive parts. This also allows, for example, guided electromagnetic waves propagating along transmission media having no more than a single conductor (for example, electromagnetic waves propagating along the surface of a single bare conductor or along the surface of a single insulated conductor or wholly or partially within the insulation of an insulated conductor Propagating electromagnetic waves) transmission. Even if the transmission medium includes one or more conductive parts and guided electromagnetic waves propagating along the transmission medium sometimes generate currents flowing in the one or more conductive parts in the direction of the guided electromagnetic waves, such guided electromagnetic waves may Propagates along the transmission medium from the sending device to the receiving device without the flow of the opposite current on the electrical return path from the receiving device back to the sending device. Accordingly, propagation of such guided electromagnetic waves may be referred to as propagation via a single transmission line or propagation via a surface wave transmission line.

In a non-limiting illustration, consider a coaxial cable having a center conductor and a ground shield separated by an insulator. Typically, in an electrical system, a first terminal of a sending (and receiving) device may be connected to a center conductor, and a second terminal of a sending (and receiving) device may be connected to a ground shield. If the transmitting device injects an electrical signal in the center conductor via the first terminal, said electrical signal will propagate along the center conductor, sometimes causing a forward current and corresponding flow of electrons in the center conductor and causing backflow in the ground shield Opposite flow of electric current and electrons. The same applies to two-terminal receiving equipment.

In contrast, consider a guided wave communication system such as that described in the subject disclosure, which can utilize different embodiments of transmission media (including coaxial cables, among others) to transmit and receive guided electromagnetic waves without the need for electrical circuits (ie, depending on your viewing angle, no electrical forward path or electrical return path). In one embodiment, for example, a guided wave communication system of the subject disclosure may be configured to induce a guided wave propagating along the outer surface of a coaxial cable (i.e., the outer jacket or insulation of the coaxial cable). electromagnetic waves. While a guided electromagnetic wave will induce a forward current on the grounded shield, a guided electromagnetic wave does not require a return current in the center conductor for the guided electromagnetic wave to propagate along the outer surface of the coaxial cable. In other words, while a leading electromagnetic wave will induce a forward current on the ground shield, a leading electromagnetic wave will not generate an opposing return current (or other electrical return path) in the center conductor. The same can be said for other transmission media used by guided wave communication systems for transmitting and receiving guided electromagnetic waves.

For example, a guided electromagnetic wave induced by a guided wave communication system on the outer surface of a bare conductor or an insulated conductor can propagate along the outer surface of a bare conductor or other surface of an insulated conductor without generating an opposite return current in the electrical return path . As another point of difference, in guided wave communication systems a guided electromagnetic wave propagating on the outer surface of a bare conductor is induced by the flow of electrons in the conductor itself, where most of the signal energy in the circuit is induced by the flow of electrons in the conductor itself. Only minimal forward currents are produced in , where most of the signal energy of the electromagnetic wave is concentrated over the outer surface of the bare conductor rather than inside the bare conductor. Furthermore, a guided electromagnetic wave that is confined to the outer surface of an insulated conductor produces only minimal forward current in the center conductor or conductors of the insulated conductor, wherein most of the signal energy of the electromagnetic wave is concentrated inside the insulator and/or Or in the region above the outer surface of the insulated conductor—in other words, most of the signal energy of the electromagnetic wave is concentrated outside the center conductor(s) of the insulated conductor.

Therefore, an electrical system that requires two or more conductors for carrying forward and reverse currents on separate conductors to enable the propagation of electrical signals injected by a transmitting A guided wave system that travels electromagnetic waves without the need for circuits to enable guided electromagnetic waves to propagate along the interface of a transmission medium.

Note also that the guided electromagnetic waves described in the subject disclosure may have an electromagnetic field structure located primarily or substantially outside the transmission medium so as to be confined to or guided by the transmission medium and so as to be outside the transmission medium. Propagate a non-insignificant distance on or along the outer surface of the transmission medium. In other embodiments, the guided electromagnetic wave may have an electromagnetic field structure predominantly or substantially inside the transmission medium, so as to be confined to or guided by the transmission medium, and so as to propagate a non-insignificant distance within the transmission medium. In other embodiments, the guided electromagnetic wave may have an electromagnetic field structure partially inside and partially outside the transmission medium, so as to be confined to or guided by the transmission medium, and so that propagation along the transmission medium is non-trivial distance. In embodiments, the desired electric field structure may vary based on various factors including: desired transmission distance, properties of the transmission medium itself, and environmental conditions/properties external to the transmission medium (eg, presence of rain, fog, atmospheric conditions, etc.).

Embodiments described herein relate to what may be referred to as "waveguide coupling devices," "waveguide couplers," for transmitting and/or extracting guided electromagnetic waves to and/or from transmission media at millimeter wave frequencies (e.g., 30 GHz to 300 GHz) or more simply a "coupler," "coupling device," or "transmitter," where the wavelength is related to one or more dimensions of the coupling device and/or transmission medium (such as the circumference of a wire, or other cross-sectional dimension), or lower microwave frequencies (such as 300MHz to 30GHz) may be relatively small. Transmissions can be generated to propagate as waves guided by coupling devices such as: strip lengths, arc lengths, or other lengths of dielectric material; horn, monopole, whip, slot, or other antennas; antenna arrays; magnetic resonance cavities, or other resonant couplers; coils, striplines, waveguides, or other coupling devices. In operation, the coupling device receives electromagnetic waves from a transmitter or transmission medium. The electromagnetic field structure of the electromagnetic waves may be carried inside the coupling device, outside the coupling device or some combination thereof. When the coupling device is in close proximity to the transmission medium, at least a portion of the electromagnetic wave is coupled or confined to said transmission device and continues to propagate as a guided electromagnetic wave. In a reciprocal manner, a coupling device can extract guided waves from the transmission medium and transfer these electromagnetic waves to a receiver.

According to an example embodiment, a surface wave is a type of guided wave that is guided by a surface of a transmission medium, such as the outer or exterior surface of a wire, or the wire's proximity or exposure to Another surface of another type of medium. Indeed, in an example embodiment, the surface of a wire guiding a surface wave may represent a transition surface between two different types of media. For example, in the case of bare or uninsulated wires, the surface of the wire may be the outer or outer conductive surface of the bare or uninsulated wire exposed to air or free space. As another example, in the case of insulated wire, depending on relative differences in the properties (e.g., dielectric properties) of the insulator, air, and/or conductor and also depending on the frequency or modes of propagation of the guided wave, the wire The surface of the wire may be the conductive portion of the wire that meets the insulator portion of the wire, or may otherwise be the insulator surface of the wire exposed to air or free space, or may otherwise be between the insulator surface of the wire and the insulator of the wire Any area of material between the conductive parts of conductors that partially meet.

According to example embodiments, the term "around" a wire or other transmission medium used in connection with guided waves may include fundamental guided wave propagation modes, such as guided waves with circular or substantially circular field distributions, symmetric electromagnetic field distributions ( For example, electric fields, magnetic fields, electromagnetic fields, etc.), or other fundamental patterns at least partially around a wire or other transmission medium. Furthermore, when a guided wave propagates "around" a wire or other transmission medium, it may propagate according to a guided wave propagation mode, which may include not only the fundamental wave propagation mode (e.g., the zeroth order mode), but also Additionally or alternatively include non-fundamental propagation modes, such as higher-order guided modes (e.g., 1st-order modes, 2-order modes, etc.), asymmetric modes, and/or having non-circular fields around wires or other transmission media Distributed other guided waves (eg surface waves). As used herein, the term "guided wave mode" refers to a guided wave propagation mode of a transmission medium, coupling device, or other system component of a guided wave communication system.

For example, such non-circular field distributions may be unilateral or polygonal, have one or more axial lobes characterized by relatively high field strengths and/or be characterized by relatively low field strengths, zero field strengths, or substantially One or more nulls or null regions of upper zero field strength. Further, according to example embodiments, the field distribution may otherwise vary around the wire according to the azimuthal orientation such that one or more angular regions around the wire have a higher Electric or magnetic field strength (or a combination thereof). It should be appreciated that the relative orientation or position of the higher order or asymmetric modes of the guided wave may vary as the guided wave travels along the wire.

As used herein, the term "millimeter wave" may refer to electromagnetic waves/signals falling within the "millimeter wave frequency band" of 30 GHz to 300 GHz. The term "microwave" may refer to electromagnetic waves/signals falling within the "microwave frequency band" of 300 MHz to 300 GHz. The term "radio frequency" or "RF" may refer to electromagnetic waves/signals falling within the "radio frequency band" ranging from 10 kHz to 1 THz. It should be appreciated that wireless signals, electrical signals, and guided electromagnetic waves as described in the subject disclosure may be configured to operate over any desired frequency range, such as, for example, within millimeter wave and/or microwave frequency bands, above or below the frequency. In particular, when the coupling device or the transmission medium comprises a conductive element, the frequency of the guided electromagnetic wave carried by the coupling device and/or propagating along the transmission medium may be below the average collision frequency of electrons in the conductive element. Further, the frequency of the guided electromagnetic wave carried by the coupling device and/or propagating along the transmission medium may be a non-optical frequency, eg radio frequency below the optical frequency range starting at 1 THz.

As used herein, the term "antenna" may refer to a device that is part of a transmission system or a reception system for transmitting/radiating or receiving wireless signals.

In accordance with one or more embodiments, a method includes: receiving a plurality of communication signals; and generating, by a transmitting device, a wireless signal for inducing a plurality of electromagnetic waves at least partially confined to an insulating transmission medium based on the plurality of communication signals , wherein the plurality of electromagnetic waves propagate along the insulating transmission medium without an electrical return path, wherein each electromagnetic wave of the plurality of electromagnetic waves carries at least one communication signal of the plurality of communication signals , wherein the plurality of electromagnetic waves has a signal multiplexing configuration that reduces interference between the plurality of electromagnetic waves and enables a receiving device to retrieve the at least one communication signal.

According to one or more embodiments, a transmitter station may include: a generator; and circuitry coupled to the generator. The controller performs operations comprising: receiving a plurality of communication signals; and generating a signal based on the plurality of communication signals that induces a plurality of electromagnetic waves at least partially confined to a dielectric layer of a transmission medium, wherein the Each of the plurality of electromagnetic waves conveys at least one of the plurality of communication signals, and wherein the plurality of electromagnetic waves has a signal multiplexing configuration that reduces interference.

According to one or more embodiments, an apparatus includes: means for receiving a plurality of communication signals; and means for generating a signal from the plurality of communication signals that induces a plurality of electromagnetic waves at least partially confined to a dielectric material, Wherein, each of the plurality of electromagnetic waves transmits at least one communication signal of the plurality of communication signals, wherein the plurality of electromagnetic waves has a multiplexing configuration, and the multiplexing configuration reduces the number of communication signals between the plurality of electromagnetic waves. Interference between.

Referring now to FIG. 1 , there is shown a block diagram 100 illustrating an example, non-limiting embodiment of a guided wave communication system. In operation, transmission device 101 receives one or more communication signals 110 comprising data from a communication network or other communication device and generates guided waves 120 to communicate the data to transmission device 102 via transmission medium 125 . Transmission device 102 receives guided waves 120 and converts them into communication signals 112 comprising data for transmission to a communication network or other communication device. Guided wave 120 can be modulated to via modulation techniques such as Phase Shift Keying, Frequency Shift Keying, Quadrature Amplitude Modulation, Amplitude Modulation, Multicarrier Modulation such as Orthogonal Frequency Division Multiplexing Multiple access techniques such as time division multiplexing, code division multiplexing, multiplexing via different wave propagation modes, and via other modulation and access strategies to transmit data.

The one or more communication networks may include wireless communication networks, such as mobile data networks, cellular voice and data networks, wireless local area networks (e.g., WiFi or 802.xx networks), satellite communication networks, personal area networks, or other wireless networks . The one or more communication networks may also include a wired communication network, such as a telephone network, Ethernet, local area network, wide area network (such as the Internet), broadband access network, cable TV network, fiber optic network, or other wired network. Communication devices can include network edge devices, bridging devices or residential gateways, set-top boxes, broadband modems, telephone adapters, access points, base stations or other fixed communication devices, mobile communication devices such as automotive gateways or cars, laptops, tablets computer, smartphone, cellular phone, or other communication device.

In an example embodiment, the guided wave communication system 100 may operate in a bi-directional manner, wherein the transmission device 102 receives one or more communication signals 112 including other data from a communication network or device and generates guided waves 122 to communicate via the transmission medium 125 transmits the other data to the transmission device 101. In this mode of operation, the transmission device 101 receives the guided waves 122 and converts them into a communication signal 110 including other data for transmission to a communication network or device. Guided wave 122 can be modulated to via modulation techniques such as Phase Shift Keying, Frequency Shift Keying, Quadrature Amplitude Modulation, Amplitude Modulation, Multicarrier Modulation such as Orthogonal Frequency Division Multiplexing Multiple access techniques such as time division multiplexing, code division multiplexing, multiplexing via different wave propagation modes, and via other modulation and access strategies to transmit data.

Transmission medium 125 may include an electrical cable having at least one interior portion surrounded by a dielectric material, such as an insulator or other dielectric covering, coating, or other dielectric material, having an outer surface and a corresponding perimeter. In an example embodiment, the transmission medium 125 operates as a single-conductor transmission line to direct the transmission of electromagnetic waves. When the transmission medium 125 is implemented as a single-wire transmission system, it may include conductive wires. The wires may be insulated or uninsulated, and may be single or multi-stranded (eg, braided). In other embodiments, transmission medium 125 may comprise conductors of other shapes or configurations, including wire harnesses, cables, rods, tracks, pipes. In addition, transmission medium 125 may include non-conductors, such as dielectric tubes, rods, tracks, or other dielectric members; combinations of conductors and dielectric materials, conductors without dielectric materials, or other guided wave propagation media. It should be noted that transmission medium 125 may otherwise comprise any of the previously discussed transmission media.

Further, as previously discussed, guided waves 120 and 122 may be contrasted with radio transmission over free space/air or conventional propagation of power or signals via conductors of wires through a circuit. In addition to the propagation of guided waves 120 and 122, transmission medium 125 may optionally contain one or more wires that propagate electrical power or other communication signals in a conventional manner as part of one or more electrical circuits.

Referring now to FIG. 2 , there is shown a block diagram 200 illustrating an example non-limiting embodiment of a transmission device. The transmission device 101 or 102 includes a communication interface (I/F) 205 , a transceiver 210 and a coupler 220 .

In an example of operation, communication interface 205 receives communication signal 110 or 112 including data. In various embodiments, the communication interface 205 may include a communication interface for communication according to wireless standard protocols (such as LTE or other cellular voice and data protocols, WiFi or 802.11 protocols, WIMAX protocols, ultra-wideband protocols, Bluetooth protocols, Zigbee protocols, Direct Broadcast Satellite (DBS) DBS) or other satellite communication protocols, or other wireless protocols) wireless interface for receiving wireless communication signals. Additionally or alternatively, the communication interface 205 includes a protocol based on the Ethernet protocol, the Universal Serial Bus (USB) protocol, the Data Over Cable Service Interface Specification (DOCSIS) protocol, the Digital Subscriber Line (DSL) protocol, the Firewire (IEEE 1394) protocol, or other wired Wired interface for protocol operation. In addition to standards-based protocols, communication interface 205 may also operate in conjunction with other wired or wireless protocols. Furthermore, the communication interface 205 may optionally operate in conjunction with a protocol stack comprising multiple protocol layers, including a MAC protocol, a transport protocol, an application protocol, and the like.

In an example of operation, transceiver 210 generates electromagnetic waves based on communication signal 110 or 112 to communicate data. The electromagnetic waves have at least one carrier frequency and at least one corresponding wavelength. The carrier frequency may be in the millimeter wave frequency band of 30GHz to 300GHz (such as 60GHz), or in the range of 30GHz to 40GHz, or in the lower frequency band range of 300MHz to 30GHz in the microwave frequency range (such as 26GHz to 30GHz, 11GHz, 6GHz or 3GHz), although it will be appreciated that other carrier frequencies are possible in other embodiments. In one mode of operation, the transceiver 210 only upconverts the one or more communication signals 110 or 112 for electromagnetic signals in the microwave or millimeter wave frequency bands as directed or confined by the transmission medium 125 to the The transmission medium guides electromagnetic waves for transmission. In another mode of operation, the communication interface 205 either converts the communication signal 110 or 112 to a baseband or near-baseband signal or extracts data from the communication signal 110 or 112, and the transceiver 210 utilizes the data, baseband or near-baseband The signal modulates a high-frequency carrier for transmission. It should be appreciated that the transceiver 210 may modulate data received via the communication signal 110 or 112 to maintain one or more of the communication signals 110 or 112 by encapsulation in the payload of a different protocol or by simple frequency shifting. data communication protocol. In the alternative, transceiver 210 may otherwise convert data received via communication signal 110 or 112 into a protocol different from the one or more data communication protocols of communication signal 110 or 112 .

In an example of operation, coupler 220 couples electromagnetic waves to transmission medium 125 as guided electromagnetic waves for transmitting the one or more communication signals 110 or 112 . While the previous description has focused on the operation of transceiver 210 as a transmitter, transceiver 210 is also operable to receive electromagnetic waves carrying other data from a single-wire transmission medium via coupler 220, and to generate communications including other data via communication interface 205. Signal 110 or 112. Embodiments are contemplated in which additional guided electromagnetic waves carry other data that also propagates along the transmission medium 125 . Coupler 220 may also couple this additional electromagnetic wave from transmission medium 125 to transceiver 210 for reception.

Transmission device 101 or 102 includes optional training controller 230 . In an example embodiment, training controller 230 is implemented by a stand-alone processor or a processor shared with one or more other components of transmission device 101 or 102 . Based on feedback data received by transceiver 210 from at least one remote transmission device coupled to receive guided electromagnetic waves, training controller 230 selects a carrier frequency, modulation scheme, and/or guided wave mode for the guided electromagnetic waves.

In an example embodiment, guided electromagnetic waves transmitted by remote transmission device 101 or 102 carry data that also propagates along transmission medium 125 . Data from the remote transmission device 101 or 102 may be generated to include feedback data. In operation, the coupler 220 also couples guided electromagnetic waves from the transmission medium 125, and the transceiver receives the electromagnetic waves and processes the electromagnetic waves to extract feedback data.

In an example embodiment, the training controller 230 operates based on the feedback data to evaluate a plurality of candidate frequencies, modulation schemes and/or transmission modes, thereby selecting a carrier frequency, modulation scheme and/or transmission mode to enhance performance (such as throughput, Signal strength), reduce propagation loss, etc.

Consider the following example: by sending a plurality of guided waves as test signals (such as pilot waves) or other test signals at candidate modes corresponding to a plurality of candidate frequencies and/or directed at the remote transmission device 102 coupled to the transmission medium 125 to the As described above for the remote transmission device, the transmission device 101 begins to operate under the control of the training controller 230 . The guided waves may additionally or alternatively include test data. The test data may be indicative of specific candidate frequencies and/or guided wave modes of the signal. In an embodiment, the training controller 230 at the remote transmission device 102 receives test signals and/or test data from any appropriately received guided waves and determines the best candidate frequencies and/or guided wave modes, a set of possible Accepted candidate frequencies and/or guided wave modes, or a ranking order of candidate frequencies and/or guided wave modes. This selection of candidate frequency(s) or/and steering pattern(s) is performed by training controller 230 based on one or more optimization criteria such as received signal strength, bit error rate, packet error rate, signal-to-noise ratio , propagation loss, etc.) generated. The training controller 230 generates feedback data indicative of selection of candidate frequency(s) or/and guided wave mode(s) and sends the feedback data to the transceiver 210 for transmission to the transmission device 101 . Transmitting devices 101 and 102 may then communicate data to each other based on selection of candidate frequency(s) or/and guided wave pattern(s).

In other embodiments, pilot electromagnetic waves containing test signals and/or test data are reflected, relayed, or otherwise looped back to transmission device 101 by remote transmission device 102 for transmission of these waves by initiating The training controller 230 of the device 101 receives and analyzes it. For example, the transmission device 101 may send a signal to the remote transmission device 102 to initiate a test mode in which a physical reflector is connected to the line, the termination impedance is changed to cause reflection, and the loopback mode is turned on to couple the electromagnetic wave back to the source transmission device 102 , and/or enable repeater mode to amplify the electromagnetic waves and retransmit them back to the source transmission device 102 . The training controller 230 at the source transmission device 102 receives test signals and/or test data from any appropriately received guided waves and determines a selection of candidate frequency(s) or/and guided wave mode(s).

Although the above process has been described when starting up or initializing the mode of operation, each transmission device 101 or 102 can also transmit test signals at other times or continuously, evaluate candidate frequencies or guided wave patterns via non-test transmissions such as normal transmissions , or otherwise evaluate candidate frequencies or guided wave modes. In an example embodiment, the communication protocol between transmission device 101 and transmission device 102 may include an on-demand or periodic test mode in which full or more limited testing of a subset of candidate frequencies and guided wave patterns is tested and evaluated. In other modes of operation, re-entry into this test mode may be triggered by degradation in performance due to disturbances, weather conditions, and the like. In an example embodiment, the receiver bandwidth of transceiver 210 is either wide enough or swept to receive all candidate frequencies or may be selectively adjusted by training controller 230 into a training mode in which transceiver 210 The receiver bandwidth is wide enough or swept to receive all candidate frequencies.

Referring now to FIG. 3 , a graphical diagram 300 illustrating an example, non-limiting embodiment of an electromagnetic field distribution is shown. In this embodiment, the transmission medium 125 in air includes an inner conductor 301 and an insulating sheath 302 of dielectric material, as shown in cross-section. Diagram 300 includes different gray levels representing different electromagnetic field strengths generated by propagation of guided waves having asymmetric and non-fundamental guided wave modes.

Specifically, the electromagnetic field distribution corresponds to a mode "sweet spot" that enhances guided electromagnetic wave propagation along the insulating transmission medium and reduces end-to-end transmission loss. In this particular mode, electromagnetic waves are guided by the transmission medium 125 to propagate along the outer surface of the transmission medium, in this case the outer surface of the insulating sheath 302 . Electromagnetic waves are partly embedded in the insulator and partly radiated on the outer surface of the insulator. In this way, electromagnetic waves are "lightly" coupled to the insulator to enable electromagnetic wave propagation at long distances with low propagation loss.

As shown, the guided waves have a field structure located primarily or substantially outside the transmission medium 125 used to guide the electromagnetic waves. The region inside conductor 301 has little or no field. Also, the area inside the insulating sheath 302 has low field strength. Most of the electromagnetic field strength is distributed in the lobes 304 located at the outer surface of the insulating sheath 302 and in close proximity thereto. The presence of asymmetric guided wave modes is shown by the high electromagnetic field strengths at the top and bottom of the outer surface of the insulating sheath 302 (in the orientation of the schematic diagram)—compared to very small fields on the sides of the insulating sheath 302 strong opposite.

The example shown corresponds to an electromagnetic wave at 38 GHz guided by a wire with a diameter of 1.1 cm and a dielectric insulator with a thickness of 0.36 cm. Because the electromagnetic waves are guided by the transmission medium 125, and most of the field strength is concentrated in the air outside the insulating sheath 302 within a limited distance of the outer surface, the guided waves can propagate longitudinally down the transmission medium 125 with very low loss . In the example shown, this "finite distance" corresponds to a distance from the outer surface that is less than half the largest cross-sectional dimension of the transmission medium 125 . In this case, the largest cross-sectional dimension of the wire corresponds to an overall diameter of 1.82 cm, however, this value may vary with the size and shape of the transmission medium 125 . For example, if the transmission medium 125 takes the shape of a rectangle with a height of 0.3 cm and a width of 0.4 cm, the diagonal of the largest cross-sectional dimension would be 0.5 cm and the corresponding finite distance would be 0.25 cm. The dimension of the region containing most of the field strength also varies with frequency and generally increases with decreasing carrier frequency.

It should also be noted that components of the guided wave communication system, such as couplers and transmission media, may have their own cutoff frequencies for each guided wave mode. The cutoff frequency generally states the lowest frequency at which a particular guided wave mode is designed to be supported by that particular component. In an example embodiment, the particular asymmetric mode of propagation shown is induced on the transmission medium 125 by electromagnetic waves whose frequencies fall within a limited range (such as Fc to 2Fc) of the lower cutoff frequency Fc of this particular asymmetric mode. )Inside. The lower limit cutoff frequency Fc is specific to the characteristics of the transmission medium 125 . For the embodiment shown that includes an inner conductor 301 surrounded by an insulating sheath 302, this cutoff frequency may vary based on the dimensions and properties of the insulating sheath 302, and potentially the inner conductor 301, and can be determined experimentally. was determined to have the desired mode pattern. It should be noted, however, that a similar effect can be found for hollow dielectrics or insulators without inner conductors. In this case, the cutoff frequency may vary based on the dimensions and properties of the hollow dielectric or insulator.

At frequencies below the lower cut-off frequency, asymmetric modes are difficult to induce in the transmission medium 125 and propagate only negligible distances. As the frequency increases above a limited frequency range about the cutoff frequency, the asymmetric mode is shifted more and more inside the insulating sheath 302 . At frequencies much higher than the cut-off frequency, the field strength is no longer concentrated outside the insulating sheath, but mainly inside the insulating sheath 302 . Although the transmission medium 125 provides stronger guidance for the electromagnetic waves and propagation is still possible, the range is more limited due to the increased loss of propagation within the insulating sheath 302 - as opposed to the surrounding air.

Referring now to FIG. 4 , a graphical sketch 400 illustrating an example, non-limiting embodiment of an electromagnetic field distribution is shown. In particular, a cross-sectional schematic 400 similar to that of FIG. 3 is shown with common numerals used to refer to similar elements. The example shown corresponds to a wave at 60 GHz guided by a wire with a diameter of 1.1 cm and a dielectric insulator with a thickness of 0.36 cm. Since the frequency of the guided wave is above a limited range of cut-off frequencies for this particular asymmetric mode, the majority of the field strength has shifted towards the interior of the insulating sheath 302 . Specifically, the field strength is mainly concentrated inside the insulating sheath 302 . Although the transmission medium 125 provides stronger guidance to the electromagnetic waves and propagation is still possible, when compared to the embodiment of FIG.

Referring now to FIG. 5A , a graphical diagram illustrating an example non-limiting embodiment of a frequency response is shown. Specifically, the diagram 500 presents a graph of end-to-end loss (in dB) as a function of frequency, covering the electromagnetic field distribution 510, 520 and 530 at three points with 200 cm of insulated medium voltage wire. In each electromagnetic field distribution, the boundary between the insulator and the surrounding air is indicated by reference numeral 525 .

As discussed in connection with FIG. 3, an example of the desired asymmetric propagation mode shown is induced on the transmission medium 125 by electromagnetic waves whose frequency falls within the lower cut-off frequency Fc of the transmission medium for this particular asymmetric mode. within a limited range (such as Fc to 2Fc). Specifically, the electromagnetic field distribution 520 at 6 GHz falls within this mode "sweet spot", which enhances electromagnetic wave propagation along the insulating transmission medium and reduces end-to-end transmission loss. In this particular mode, the guided wave is partly embedded in the insulator and partly radiates on the outer surface of the insulator. In this way, electromagnetic waves are "lightly" coupled to the insulator to enable guided electromagnetic wave propagation at long distances with low propagation loss.

At lower frequencies, represented by the electromagnetic field distribution 510 at 3 GHz, the asymmetric mode radiates more, resulting in higher propagation losses. At higher frequencies, represented by the electromagnetic field distribution 530 at 9 GHz, the asymmetric modes are increasingly shifted inwards of the insulating sheath, providing too much absorption, again resulting in higher propagation losses.

Referring now to FIG. 5B , there is shown a graphical diagram 550 illustrating an example non-limiting embodiment of a longitudinal cross-section of a transmission medium 125 , such as an insulated wire, depicting a guided electromagnetic wave field at various operating frequencies. As shown in diagram 556, when the pilot electromagnetic wave is approximately at the cutoff frequency ( _fc ) corresponding to the "sweet spot" of the mode, the pilot electromagnetic wave is loosely coupled to the insulated wire, thereby reducing absorption, And the field of the guided electromagnetic wave is sufficiently confined so as to reduce the amount of radiation into the environment (eg air). Due to the lower absorption and radiation of the guided electromagnetic wave field, the propagation loss is therefore lower, allowing the guided electromagnetic wave field to travel longer distances.

As shown in diagram 554, propagation loss increases as the operating frequency of the guided electromagnetic wavefield increases above approximately twice the cutoff frequency ( _fc ) - or a range known as the "sweet spot". More field strength of the electromagnetic wave is driven within the insulating layer, increasing the propagation loss. At frequencies much higher than the cut-off frequency ( _fc ), the guided electromagnetic wave is strongly confined to the insulated wire due to the field emitted by the guided electromagnetic wave being concentrated in the insulation of the wire, as shown in sketch 552 of. This, in turn, further creates propagation losses due to the absorption of the guided electromagnetic waves by the insulating layer. Similarly, when the operating frequency of the pilot electromagnetic wave is substantially below the cutoff frequency (f _c ), propagation loss increases, as shown in diagram 558 . At frequencies much lower than the cutoff frequency (f _c ), guided electromagnetic waves are weakly (or nominally) confined to insulated wires, and thus tend to radiate into the environment (e.g., air), which in turn Propagation loss occurs due to radiation of guided electromagnetic waves.

Referring now to FIG. 6 , a graphical sketch 600 illustrating an example, non-limiting embodiment of an electromagnetic field distribution is shown. In this embodiment, transmission medium 602 is bare wire, as shown in cross-section. Diagram 300 includes different gray levels representing different electromagnetic field strengths generated by guided waves with symmetric and non-fundamental guided wave modes propagating at a single carrier frequency.

In this particular mode, electromagnetic waves are guided by the transmission medium 602 to propagate along the outer surface of the transmission medium, in this case the outer surface of the bare wire. Electromagnetic waves are "lightly" coupled to the wire to enable electromagnetic wave propagation over long distances with low propagation loss. As shown, the guided waves have a field structure substantially outside of the transmission medium 602 used to guide the electromagnetic waves. The region inside conductor 602 has little or no field.

Referring now to FIG. 7 , a block diagram 700 illustrating an example non-limiting embodiment of an arc coupler is shown. In particular, a coupling device for use in a transmission device such as the transmission device 101 or 102 presented in connection with Fig. 1 is presented. The coupling device includes an arc coupler 704 coupled to a transmitter circuit 712 and a termination or damper 714 . The arc coupler 704 can be made of a dielectric material or other low loss insulator (e.g., Teflon, polyethylene, etc.), or a conductive (e.g., metal, non-metal, etc.) material, or any combination of the foregoing. combination. As shown, the arc coupler 704 operates as a waveguide and has a wave 706 propagating as a guided wave around the waveguide surface of the arc coupler 704 . In the illustrated embodiment, at least a portion of arc coupler 704 may be placed adjacent to conductor 702 or other transmission medium, such as transmission medium 125, to facilitate communication between arc coupler 704 and conductor 702 or other transmission medium. coupling, as described herein, to launch guided waves 708 on the wire. The arc coupler 704 can be positioned such that a portion of the curved arc coupler 704 is tangent to the wire 702 and is parallel or substantially parallel. The portion of the arc coupler 704 that is parallel to the wire may be the vertex of the curve, or any point where the tangent of the curve is parallel to the wire 702 . When arcuate coupler 704 is so positioned or placed, wave 706 traveling along arcuate coupler 704 is at least partially coupled to conductor 702 and is guided as wave 708 around or near the conductor surface of conductor 702 and longitudinally along conductor 702 to spread. Guided waves 708 may be characterized as surface waves or other electromagnetic waves guided by or confined to wire 702 or other transmission medium.

The portion of wave 706 that is not coupled to wire 702 propagates as wave 710 along curved coupler 704 . It should be appreciated that arc coupler 704 may be configured and arranged in a variety of positions with respect to conductor 702 to achieve a desired level of coupling or decoupling of wave 706 to conductor 702 . For example, the curvature and/or length of the arcuate coupler 704 parallel or substantially parallel to the conductor 702, as well as its separation distance from the conductor (in an embodiment, this may include a zero separation distance) may vary without departing from example The case of the example varies. Likewise, the arrangement of arcuate coupler 704 with respect to wire 702 can be based on the corresponding intrinsic properties of wire 702 and arcuate coupler 704 (e.g., thickness, composition, electromagnetic properties, etc.), as well as the properties of waves 706 and 708 (e.g., frequency , energy levels, etc.) considerations.

Even as lead 702 bends and buckles, guided wave 708 remains parallel or substantially parallel to lead 702 . Bends in the wire 702 can increase transmission loss, which also depends on wire diameter, frequency and material. If the dimensions of arc coupler 704 are chosen for efficient power transfer, most of the power in wave 706 is diverted to wire 702 , leaving little power in wave 710 . It should be appreciated that the guided wave 708 can still be multimodal in nature (discussed herein), including having modes that are not fundamental or asymmetrical, while traveling along a path that is parallel or substantially parallel to the wire 702, With or without fundamental transmission mode. In embodiments, non-fundamental or asymmetric modes may be used to minimize transmission loss and/or obtain increased propagation distance.

It should be noted that the term "parallel" is generally a geometric construction, which is often not precisely achievable in practical systems. Accordingly, the term "parallel" as used in this disclosure when used to describe the embodiments disclosed in this disclosure indicates an approximate rather than an exact configuration. In an embodiment, substantially parallel may include approximation within 30 degrees of true parallel in all dimensions.

In an embodiment, wave 706 may exhibit one or more modes of wave propagation. The curved coupler pattern may depend on the shape and/or design of the coupler 704 . The one or more arcuate coupler modes of wave 706 may generate, influence, or impinge on one or more wave propagation modes of guided wave 708 propagating along wire 702 . However, it should be particularly noted that the guided wave mode present in guided wave 706 may be the same as or different from that of guided wave 708 . In this way, one or more guided wave modes of guided wave 706 may not be transferred to guided wave 708 , and further, one or more guided wave modes of guided wave 708 may not already be present in guided wave 706 . It should also be noted that the cutoff frequency of arc coupler 704 for a particular guided wave mode may be different than the cutoff frequency of wire 702 or other transmission medium for the same mode. For example, while the wire 702 or other transmission medium can operate slightly above its cutoff frequency for a particular guided wave mode, the arc coupler 704 can be operated much higher than its cutoff frequency for the same mode in order to reduce losses, Operate slightly below its cutoff frequency for this same mode to eg induce greater coupling and power transfer, or at some other point relative to the arc coupler's cutoff frequency for this mode.

In an embodiment, the mode of wave propagation on the wire 702 may be similar to the mode of the curved coupler in that waves 706 and 708 both propagate around the outside of the curved coupler 704 and the wire 702, respectively. In some embodiments, when wave 706 is coupled to wire 702, the modes may change form, or new modes may be created or generated due to the coupling between arc coupler 704 and wire 702. For example, differences in size, material, and/or impedance of arc coupler 704 and wire 702 may create additional modes not present in arc coupler modes and/or may suppress some arc coupler modes. Wave propagation modes may include fundamental transverse electromagnetic modes (quasi-TEM ₀₀ ) in which only small electric and/or magnetic fields extend in the direction of propagation, and the electric and magnetic fields extend radially outward while the guided wave propagates along the wire. This guided wave mode may be toroidal, where few of these electromagnetic fields exist within arc coupler 704 or wire 702 .

Waves 706 and 708 may include fundamental TEM modes with fields extending radially outward, and also include other non-fundamental (eg, asymmetric, higher order, etc.) modes. Although specific modes of wave propagation are discussed above, based on the frequency employed, the design of the arc coupler 704, the dimensions and composition of the wire 702 and its surface properties, its insulation (if present), the electromagnetic properties of the surrounding environment, etc. , other wave propagation modes are equally possible, such as transverse electric (TE) modes and transverse magnetic (TM) modes. It should be noted that, depending on the frequency, the electrical and physical properties of the wire 702, and the particular wave propagation mode generated, the guided wave 708 can travel along an oxidized uninsulated wire, an unoxidized uninsulated wire, a conductive surface of an insulated wire, and and/or run along the insulated surface of an insulated wire.

In an embodiment, the diameter of the arc coupler 704 is smaller than the diameter of the wire 702 . Arc coupler 704 supports a single waveguide mode constituting wave 706 for the mmWave band wavelengths used. This single waveguide mode can change when it couples to the wire 702 as a guided wave 708 . If the arc coupler 704 is larger, more than one waveguide mode can be supported, but these additional waveguide modes may not couple as efficiently to the wire 702 and may result in higher coupling losses. However, in some alternative embodiments, the diameter of the arc coupler 704 may be equal to or greater than the diameter of the wire 702, for example, where higher coupling losses are desired or when used in conjunction with other techniques to otherwise reduce coupling losses (eg, impedance matching by tapering, etc.).

In an embodiment, the wavelengths of waves 706 and 708 are comparable in size, or smaller than the circumference of arc coupler 704 and wire 702 . In an example, if the wire 702 has a diameter of 0.5 cm and a corresponding circumference of about 1.5 cm, then the transmitted wavelength is about 1.5 cm or less, corresponding to a frequency of 70 GHz or greater. In another embodiment, suitable frequencies for the transmission and carrier signals are in the range of 30 GHz to 100 GHz, possibly about 30 GHz to 60 GHz, and in one example about 38 GHz. In embodiments, waves 706 and 708 may appear to propagate over sufficient distances to support the various Multiwave propagation modes of communication systems, including fundamental and/or non-fundamental (symmetric and/or asymmetric) modes. Accordingly, waves 706 and 708 may include more than one type of electric and magnetic field configurations. In an embodiment, as the guided wave 708 propagates along the wire 702, the electrical and magnetic field configuration will remain the same from one end of the wire 702 to the other. In other embodiments, the electric field configuration and magnetic field configuration may change as the guided wave 708 propagates along the wire 702 when the guided wave 708 encounters interference (distortion or obstruction) or loses energy due to transmission loss or scattering.

In an embodiment, arc coupler 704 may be constructed of nylon, Teflon, polyethylene, polyamide, or other plastic. In other embodiments, other dielectric materials are possible. The wire surface of wire 702 may be metal with a bare metal surface, or may be insulated using a plastic, dielectric, insulator, or other coating, jacket, or housing. In embodiments, dielectric or other non-conductive/insulated waveguides may be paired with bare/metallic or insulated wires. In other embodiments, metal and/or conductive waveguides may be paired with bare/metal wires or insulated wires. In an embodiment, an oxide layer on the bare metal surface of the wire 702 (eg, resulting from exposure of the bare metal surface to oxygen/air) may also provide insulating or dielectric properties similar to those provided by some insulators or sheathing.

It should be noted that the graphical representations of waves 706, 708, and 710 are only intended to illustrate the principle of wave 706 inducing or otherwise launching guided wave 708 on wire 702, eg, operating as a single wire transmission line. Wave 710 represents the portion of wave 706 that remains on arc coupler 704 after generation of guided wave 708 . The actual electric and magnetic fields generated as a result of such wave propagation may depend on the frequency employed, the particular wave propagation mode or modes, the design of the arc coupler 704, the dimensions and composition of the wire 702, and its surface properties , its optional insulation, the electromagnetic properties of the surrounding environment, etc.

It should be noted that the arc coupler 704 may include a termination circuit or damper 714 at the ends of the arc coupler 704 that may absorb residual radiation or energy from the wave 710 . Termination circuit or damper 714 may prevent and/or minimize residual radiation or energy from wave 710 that reflects back toward transmitter circuit 712 . In an embodiment, the termination circuit or damper 714 may include a termination resistor and/or other components that perform impedance matching to attenuate reflections. In some embodiments, if the coupling efficiency is high enough, and/or the wave 710 is small enough, then it may not be necessary to use a termination circuit or damper 714 . For simplicity, these transmitter circuits 712 and termination circuits or dampers 714 may not be depicted in other figures, but in those embodiments, transmitter circuits and termination circuits or dampers may be used.

Additionally, while a single arc coupler 704 is shown generating a single guided wave 708, multiple arc couplers 704 placed at different points along the wire 702 and/or at different azimuthal orientations around the wire may be employed to provide A plurality of guided waves 708 are generated and received at the same or different frequencies, at the same or different phases, and in the same or different wave propagation modes.

FIG. 8 is a block diagram 800 showing an example non-limiting embodiment illustrating an arc coupler. In the illustrated embodiment, at least a portion of coupler 704 may be placed adjacent to wire 702 or other transmission medium, such as transmission medium 125, to facilitate coupling between arcuate coupler 704 and wire 702 or other transmission medium , thereby extracting a portion of guided wave 806 as guided wave 808 as described herein. The arc coupler 704 can be positioned such that a portion of the curved arc coupler 704 is tangent to the wire 702 and is parallel or substantially parallel. The portion of the arc coupler 704 that is parallel to the wire may be the vertex of the curve, or any point where the tangent of the curve is parallel to the wire 702 . When arc coupler 704 is so positioned or placed, wave 806 traveling along conductor 702 is at least partially coupled to arc coupler 704 and propagates along arc coupler 704 as guided wave 808 to a receiving device (not expressly shown). out). The portion of wave 806 that is not coupled to the arc coupler propagates as wave 810 along wire 702 or other transmission medium.

In an embodiment, wave 806 may exhibit one or more modes of wave propagation. The curved coupler pattern may depend on the shape and/or design of the coupler 704 . One or more modes of guided wave 806 may generate, influence, or impinge on one or more guided wave modes of guided wave 808 propagating along arc coupler 704 . However, it should be particularly noted that the guided wave mode present in guided wave 806 may be the same as or different from that of guided wave 808 . In this way, one or more guided wave modes of guided wave 806 may not be transferred to guided wave 808 , and further, one or more guided wave modes of guided wave 808 may not already be present in guided wave 806 .

Referring now to FIG. 9A , a block diagram 900 illustrating an example, non-limiting embodiment of a stub coupler is shown. In particular, a coupling device comprising a stub coupler 904 for use in a transmission device such as the transmission device 101 or 102 presented in connection with Fig. 1 is presented. The stub coupler 904 can be made of a dielectric material or other low loss insulator (e.g., Teflon, polyethylene, etc.), or a conductive (e.g., metal, non-metal, etc.) material, or a combination of the foregoing. random combination. As shown, the stub coupler 904 operates as a waveguide and has a wave 906 propagating as a guided wave around the waveguide surface of the stub coupler 904 . In the illustrated embodiment, at least a portion of stub coupler 904 may be placed adjacent to wire 702 or other transmission medium, such as transmission medium 125, so as to facilitate communication of stub coupler 904 with wire 702 or other transmission medium. coupled as described herein to launch guided waves 908 on the wire.

In an embodiment, the stub coupler 904 is curved, and the ends of the stub coupler 904 may be tied, fastened, or otherwise mechanically coupled to the wire 702 . When the ends of the stub coupler 904 are secured to the wire 702 , the ends of the stub coupler 904 are parallel or substantially parallel to the wire 702 . Alternatively, another portion of the dielectric waveguide beyond the end may be fastened or coupled to the wire 702 such that the fastened or coupled portion is parallel or substantially parallel to the wire 702 . Fastener 910 may be a nylon cable tie or other type of non-conductive/dielectric material separate from stub coupler 904 or constructed as an integral component of stub coupler 904 . The stub coupler 904 may be adjacent to the wire 702 without surrounding the wire 702 .

Like the curved coupler 704 described in connection with FIG. 7 , when the stub coupler 904 is placed with its ends parallel to the wire 702, a guided wave 906 traveling along the stub coupler 904 is coupled to the wire 702, And propagate around the wire surface of the wire 702 as a guided wave 908 . In example embodiments, guided waves 908 may be characterized as surface waves or other electromagnetic waves.

It should be noted that the graphical representations of waves 906 and 908 are given only to illustrate the principle of wave 906 inducing or otherwise launching guided wave 908 on wire 702 operating, for example, as a single wire transmission line. The actual electric and magnetic fields generated as a result of such wave propagation may depend on the shape and/or design of the coupler, the relative position of the dielectric waveguide to the wire, the frequency employed, the design of the stub coupler 904, the wire 702 Dimensions and composition of the substrate, as well as one or more of its surface properties, its optional insulation, the electromagnetic properties of the surrounding environment, and the like.

In an embodiment, the ends of the stub coupler 904 may taper toward the wire 702 in order to increase coupling efficiency. Indeed, according to example embodiments of the subject disclosure, the tapering of the ends of the stub coupler 904 may provide impedance matching for the wire 702 and reduce reflections. For example, the ends of stub coupler 904 may be tapered in order to obtain a desired level of coupling between wave 906 and wave 908 as illustrated in FIG. 9A .

In an embodiment, fastener 910 may be placed such that there is a shorter length of stub coupler 904 between fastener 910 and the end of stub coupler 904 . Maximum coupling efficiency is achieved in this embodiment when the length beyond the end of the stub coupler 904 of the fastener 910 is at least a few wavelengths long for whatever frequency is being transmitted.

Turning now to FIG. 9B , there is shown a diagram 950 illustrating an example non-limiting embodiment of an electromagnetic distribution in accordance with various aspects described herein. Specifically, electromagnetic distributions are presented in two dimensions of a transmission device comprising coupler 952, shown in an example stub coupler constructed of a dielectric material. Coupler 952 couples electromagnetic waves that propagate as guided waves along the outer surface of wire 702 or other transmission medium.

The coupler 952 guides electromagnetic waves to the junction at _x0 via a symmetric guided wave mode. Although some energy of the electromagnetic wave propagating along coupler 952 is outside coupler 952 , most of the energy of this electromagnetic wave is contained within coupler 952 . The junction at x ₀ couples electromagnetic waves to the wire 702 or other transmission medium at an azimuth corresponding to the bottom of the transmission medium. This coupling induces electromagnetic waves that are directed to propagate in direction 956 via at least one guided wave mode along the outer surface of wire 702 or other transmission medium. Most of the energy of the guided electromagnetic wave is outside but very close to the outer surface of the wire 702 or other transmission medium. In the example shown, the junction at _x0 forms an electromagnetic wave propagating via both a symmetric mode and at least one asymmetric surface mode (such as the first-order mode given in connection with FIG. 3 ), the at least one Asymmetric surface modes bypass the surface of the wire 702 or other transmission medium.

It will be noted that the figures of guided waves are given only to illustrate an example of guided wave coupling and propagation. The actual electric and magnetic fields generated as a result of such wave propagation may depend on the frequency employed, the design and/or configuration of the coupler 952, the dimensions and composition of the wire 702 or other transmission medium and its surface properties, its insulation ( if present), the electromagnetic properties of the surrounding environment, etc.

Turning now to FIG. 10A , illustrated is a block diagram 1000 of an example non-limiting embodiment of a coupler and transceiver system in accordance with various aspects described herein. The system is an example of a transmission device 101 or 102 . Specifically, communication interface 1008 is an example of communication interface 205, stub coupler 1002 is an example of coupler 220, and transmitter/receiver device 1006, duplexer 1016, power amplifier 1014, low noise amplifier 1018, mixer Frequency converters 1010 and 1020 and local oscillator 1012 collectively form an example of transceiver 210.

In operation, the transmitter/receiver device 1006 transmits and receives waves (eg, to the guided waves 1004 on the stub coupler 1002). Guided waves 1004 may be used to transmit signals received from and signals transmitted to a host device, base station, mobile device, or building or other device through communication interface 1008 . Communication interface 1008 may be an integral part of system 1000 . Alternatively, communication interface 1008 may be tethered to system 1000 . The communication interface 1008 may include interfaces for interfacing to a host device, base station, mobile device, building, or utilizing various wireless signaling protocols including infrared protocols such as the Infrared Data Association (IrDA) protocol, or line-of-sight optical protocols (e.g., LTE, WiFi, WiMAX, IEEE802.xx, etc.) to the wireless interface of other devices. Communication interface 1008 may also include wired interfaces, such as fiber optic lines, coaxial cables, twisted pair cables, Category 5 (CAT-5) cables, or for communicating with host devices, base stations, mobile devices, buildings, or other devices via protocols Other suitable wired or optical media for communication, such as Ethernet protocol, Universal Serial Bus (USB) protocol, Data Cable Service Interface Specification (DOCSIS) protocol, Digital Subscriber Line (DSL) protocol, FireWire (IEEE 1394 ) protocol or other wired or optical protocols. For embodiments where system 1000 is used as a repeater, communication interface 1008 may not be necessary.

An output signal (eg, Tx) of the communication interface 1008 may be combined at a mixer 1010 with a carrier wave (millimeter wave carrier) generated by a local oscillator 1012 . Mixer 1010 may frequency shift the output signal from communication interface 1008 using heterodyning or other frequency shifting techniques. For example, the signals sent to and from the communication interface 1008 may be modulated signals, such as according to the Long Term Evolution (LTE) wireless protocol or other wireless 3G, 4G, 5G or higher voice and data protocols, Zigbee, WIMAX, Ultra Orthogonal Frequency Division Multiplexing (OFDM) signals formatted with broadband or IEEE 802.11 wireless protocols; wired protocols such as Ethernet, Universal Serial Bus (USB), Data over Cable Service Interface Specification (DOCSIS), Digital Subscriber Line (DSL) protocol, FireWire (IEEE 1394) protocol, or other wired or wireless protocols. In an example embodiment, such frequency conversion may be performed in the analog domain, and thus, frequency shifting may be performed regardless of the type of communication protocol used by the base station, mobile device, or in-building device. As new communication technologies are developed, the communication interface 1008 may be upgraded (eg, with software, firmware, and/or hardware) or replaced, and the frequency shifting and transmission means may remain, thereby simplifying upgrades. The carrier wave may then be transmitted to a power amplifier (“PA”) 1014 and may be transmitted via a transmitter receiver device 1006 via a duplexer 1016 .

Signals received from transmitter/receiver device 1006 directed toward communication interface 1008 may be separated from other signals via duplexer 1016 . The received signal may then be sent to a low noise amplifier ("LNA") 1018 for amplification. With the aid of the local oscillator 1012, the mixer 1020 may down-convert the received signal (in the mmWave band or around 38 GHz in some embodiments) to a native frequency. Communication interface 1008 may then receive the transmission at an input port (Rx).

In an embodiment, the transmitter/receiver device 1006 may comprise a cylindrical or non-cylindrical metal (e.g., which may be hollow in an embodiment, but is not necessarily drawn to scale) or other conductive or non-conductive waveguide, and The ends of the stub coupler 1002 may be placed in or near the waveguide or transmitter/receiver device 1006 so that when the transmitter/receiver device 1006 generates a transmission, the guided wave couples to the stub coupler 1002 and Propagates around the waveguide surface of the stub coupler 1002 as a guided wave 1004 . In some embodiments, guided wave 1004 may propagate partially on the outer surface of stub coupler 1002 and partially inside stub coupler 1002 . In other embodiments, guided wave 1004 may propagate substantially or entirely on the outer surface of stub coupler 1002 . In still other embodiments, guided wave 1004 may propagate substantially or completely inside stub coupler 1002 . In this latter embodiment, the guided wave 1004 may radiate at the end of the stub coupler 1002 (such as the tapered end shown in FIG. 4 ) for coupling to a transmission medium (such as the tapered end shown in FIG. 4 ). 7 wires 702). Similarly, if guided wave 1004 is incoming (coupled from wire 702 to stub coupler 1002), guided wave 1004 then enters transmitter/receiver device 1006 and couples to a cylindrical or conductive waveguide. Although the transmitter/receiver device 1006 is shown as including separate waveguides - antennas, cavity resonators, klystrons, magnetrons, traveling wave tubes, or other radiating elements may be employed to induce Guided waves, with or without a separate waveguide.

In an embodiment, the stub coupler 1002 may be constructed entirely of a dielectric material (or other suitable insulating material) without any metal or other conductive material therein. Stub coupler 1002 may be constructed of nylon, Teflon, polyethylene, polyamide, other plastics, or other materials that are non-conductive and suitable to facilitate transmission of electromagnetic waves at least in part on the outer surfaces of these materials. In another embodiment, stub coupler 1002 may include a conductive/metallic core and have an outer dielectric surface. Similarly, the transmission medium coupled to the stub coupler 1002 for propagating electromagnetic waves induced by the stub coupler 1002 or for supplying electromagnetic waves to the stub coupler 1002 may consist entirely of wires other than bare or insulated wires. Outer dielectric material (or other suitable insulating material) without any metal or other conductive material.

It should be noted that while FIG. 10A shows the opening of the transmitter-receiver device 1006 as being much wider than the stub coupler 1002, this is not to scale, and in other embodiments, the stub coupler 1002's The width is comparable to or slightly smaller than the opening of the hollow waveguide. But it is also not shown in the embodiment that the end of the coupler 1002 inserted into the transmitter/receiver device 1006 is tapered in order to reduce reflections and increase coupling efficiency.

One or more waveguide modes of the guided waves generated by the transmitter/receiver device 1006 may be coupled to the stub coupler 1002 prior to coupling to the stub coupler 1002 to induce one of the guided waves 1004 or multiple wave propagation modes. Due to the different properties of the hollow metal waveguide and the dielectric waveguide, the wave propagation mode of the guided wave 1004 may be different from the hollow metal waveguide mode. For example, the wave propagation mode of guided wave 1004 may include a fundamental transverse electromagnetic mode (quasi-TEM ₀₀ ), where only small electric and/or magnetic fields extend in the direction of propagation, and the electric and magnetic fields extend radially from stub coupler 1002. Extending outward, the guided wave propagates along the stub coupler 1002 . The fundamental transverse electromagnetic mode wave propagation mode may or may not be present inside the hollow waveguide. Thus, the hollow metal waveguide mode used by the transmitter/receiver device 1006 is a waveguide mode that can be effectively and efficiently coupled to the wave propagation mode of the stub coupler 1002 .

It should be appreciated that other configurations or combinations of transmitter/receiver devices 1006 and stub couplers 1002 are possible. For example, the stub coupler 1002' may be placed tangentially or parallel (with or without gaps) relative to the outer surface of the hollow metal waveguide of the transmitter/receiver device 1006' (corresponding circuitry not shown), As depicted by reference numeral 1000' of FIG. 10B. In another embodiment, not shown by reference numeral 1000', the stub coupler 1002' may be placed inside the hollow metal waveguide of the transmitter/receiver device 1006' without the stub coupler 1002' The axis of is aligned coaxially with the axis of the hollow metal waveguide of the transmitter/receiver device 1006'. In any of these embodiments, the guided waves generated by the transmitter/receiver device 1006' can be coupled to the surface of the stub coupler 1002' to induce guided waves on the stub coupler 1002' One or more modes of wave propagation at 1004', including fundamental modes (eg, symmetric modes) and/or non-fundamental modes (eg, asymmetric modes).

In one embodiment, the guided wave 1004' may propagate partially on the outer surface of the stub coupler 1002' and partially inside the stub coupler 1002'. In another embodiment, the guided wave 1004' may propagate substantially or entirely on the outer surface of the stub coupler 1002'. In still other embodiments, the guided wave 1004' can propagate substantially or completely inside the stub coupler 1002'. In this latter embodiment, the guided wave 1004' may radiate at the end of the stub coupler 1002' (such as the tapered end shown in FIG. 9) for coupling to a transmission medium such as wire 702 of FIG. 9).

It will also be appreciated that other configurations of transmitter/receiver device 1006 are possible. For example, a hollow metal waveguide (as depicted in FIG. The outer surfaces are placed tangentially or parallel (with or without gaps) without using the stub coupler 1002 . In this embodiment, the guided waves generated by the transmitter/receiver device 1006" may be coupled to the surface of the wire 702 to induce one or more wave propagation modes of the guided wave 908 on the wire 702, including the fundamental mode (e.g., symmetric mode) and/or non-fundamental mode (e.g., asymmetric mode). In another embodiment, wire 702 may be positioned at transmitter/receiver device 1006"' (corresponding circuitry not shown) inside the hollow metal waveguide, so that the axis of the wire 702 is coaxially (or not) aligned with the axis of the hollow metal waveguide without using the stub coupler 1002—see reference numeral 1000"' in FIG. 10B In this embodiment, the guided waves generated by the transmitter/receiver device 1006"' may be coupled to the surface of the wire 702 to induce one or more modes of wave propagation of the guided wave 908 on the wire, including the fundamental modes (eg, symmetric modes) and/or nonfundamental modes (eg, asymmetric modes).

In the 1000" and 1000"' embodiments, for a wire 702 having an insulated outer surface, the guided wave 908 may propagate partially on the outer surface of the insulator and partially inside the insulator. In an embodiment, the guided wave 908 may propagate substantially or entirely on the outer surface of the insulator, or substantially or entirely inside the insulator. In the 1000" and 1000"' embodiments, for the wire 702 being a bare conductor, the guided wave 908 may propagate partially on the outer surface of the conductor and partially inside the conductor. In another embodiment, the guided wave 908 may propagate substantially or entirely on the outer surface of the conductor.

Referring now to FIG. 11 , a block diagram 1100 illustrating an example non-limiting embodiment of a dual stub coupler is shown. In particular, a dual coupler design for use in a transmission device such as the transmission device 101 or 102 presented in connection with Fig. 1 is presented. In an embodiment, two or more couplers, such as stub couplers 1104 and 1106 , may be positioned around wire 1102 to receive guided wave 1108 . In an embodiment, one coupler is sufficient to receive the guided wave 1108 . In that case, guided wave 1108 is coupled to coupler 1104 and propagates as guided wave 1110 . If the field structure of guided wave 1108 oscillates or fluctuates around wire 1102 due to specific guided wave mode(s) or various external factors, coupler 1106 may be placed such that guided wave 1108 couples to coupler 1106 . In some embodiments, four or more couplers may be placed around a portion of the wire 1102, e.g., at 90 degrees or other spacing relative to each other, to receive guided waves that may oscillate or rotate around the wire 1102, Where guided waves have been induced at different azimuthal orientations or have eg non-fundamental or higher order modes with orientation dependent lobes and/or nulls or other asymmetries. However, it should be appreciated that less than or more than four couplers may be placed around a portion of wire 1102 without departing from example embodiments.

It should be noted that while couplers 1106 and 1104 are illustrated as stub couplers, any of the types described herein including arc couplers, antenna or horn couplers, magnetic couplers, etc. may equally be used. Other coupler designs. It will also be appreciated that while some example embodiments have shown multiple couplers around at least a portion of conductor 1102, this multiple couplers may also be considered a single coupler system having multiple coupler subcomponents a part of. For example, two or more couplers can be manufactured as a single system that can be installed around a wire in a single installation such that the couplers are relative to each other according to the single system (manually or automatically using A controllable mechanism, such as a motor or other actuator) is prepositionable or adjustable.

Receivers coupled to couplers 1106 and 1104 may use diversity combining to combine signals received from both couplers 1106 and 1104 in order to maximize signal quality. In other embodiments, if one or the other of couplers 1104 and 1106 receives a transmission above a predetermined threshold, the receiver may use selection diversity in deciding which signal to use. Further, while reception by multiple couplers 1106 and 1104 is illustrated, transmission by couplers 1106 and 1104 in the same configuration may equally occur. Specifically, various multiple-input multiple-output (MIMO) transmission and reception technologies can be used for transmission, wherein a transmission device (such as the transmission device 101 or 102 given in conjunction with FIG. 1 ) includes multiple transceivers and Multiple couplers.

It should be noted that the graphical representation of waves 1108 and 1110 is given only to illustrate the principle of guided wave 1108 inducing or otherwise launching wave 1110 on coupler 1104 . The actual electric and magnetic fields generated as a result of such wave propagation may depend on the frequency employed, the design of the coupler 1104, the dimensions and composition of the wire 1102 and its surface properties, its insulation (if any), the surrounding environment The electromagnetic properties and so on change.

Referring now to FIG. 12 , there is shown a block diagram 1200 illustrating an example, non-limiting embodiment of a repeater system. In particular, a repeater device 1210 is presented for use in a transmission device such as the transmission device 101 or 102 presented in connection with Fig. 1 . In this system, two couplers 1204 and 1214 may be placed adjacent to wire 1202 or other transmission medium such that guided wave 1205 propagating along wire 1202 is extracted by coupler 1204 as wave 1206 (e.g., as a guided wave) , and is then lifted or relayed by repeater device 1210 and launched onto coupler 1214 as wave 1216 (eg, as a guided wave). Wave 1216 may then be launched on wire 1202 and continue to propagate along wire 1202 as guided wave 1217 . In an embodiment, repeater device 1210 may receive at least a portion of the power for boosting or relaying through magnetic coupling with conductor 1202, eg, when conductor 1202 is a power line or otherwise contains a power carrying conductor. It should be noted that while couplers 1204 and 1214 are illustrated as stub couplers, any other couplers described herein including arc couplers, antenna or horn couplers, magnetic couplers, etc. may equally be used. design.

In some embodiments, repeater device 1210 may relay transmissions associated with wave 1206, and in other embodiments, repeater device 1210 may include communication interface 205 that extracts data from wave 1206 or other signals in order to supply such data or signals as communication signals 110 or 112 to and/or receive communication signals 110 from another network and/or one or more other devices or 112, and the repeater device emits a guided wave 1216 in which the received communication signal 110 or 112 is embedded. In a repeater configuration, receiver waveguide 1208 may receive wave 1206 from coupler 1204 and transmitter waveguide 1212 may transmit guided wave 1216 onto coupler 1214 as guided wave 1217 . Between the receiver waveguide 1208 and the transmitter waveguide 1212, the signal embedded in the guided wave 1206 and/or the guided wave 1216 itself may be amplified to correct for signal loss and other inefficiencies associated with guided wave communication, or the signal can be received and processed to extract the data contained within and regenerated for transmission. In an embodiment, the receiver waveguide 1208 may be configured to extract data from the signal, process the data to correct data errors using, for example, an error correction code, and regenerate an update signal using the corrected data. The transmitter waveguide 1212 may then emit a guided wave 1216 with the update signal embedded therein. In an embodiment, the signal embedded in guided wave 1206 may be extracted from the transmission and processed for communication as communication signal 110 or 112 via communication interface 205 with another network and/or one or more other devices. Similarly, communication signal 110 or 112 received by communication interface 205 may be inserted into the transmission of guided wave 1216 generated by transmitter waveguide 1212 and launched onto coupler 1214 .

It should be noted that while Figure 12 shows guided wave transmissions 1206 and 1216 respectively entering from the left and exiting from the right, this is merely a simplification and is not intended to be limiting. In other embodiments, receiver waveguide 1208 and transmitter waveguide 1212 may also function as a transmitter and receiver, respectively, allowing repeater device 1210 to be bi-directional.

In an embodiment, a repeater device 1210 may be placed where there is a discontinuity or obstruction in the wire 1202 or other transmission medium. Where conductor 1202 is a power line, these obstructions may include transformers, connections, utility poles, or other such power line equipment. The repeater device 1210 can help guided waves (eg, surface waves) jump over these obstacles on the line and boost transmission power at the same time. In other embodiments, couplers may be used to jump over obstacles without using repeater devices. In this embodiment, both ends of the coupler can be tied or fastened to the wire, thereby providing a path for the guided wave to travel without being blocked by obstacles.

Turning now to FIG. 13 , illustrated is a block diagram 1300 of an example, non-limiting embodiment of a two-way repeater in accordance with various aspects described herein. In particular, a two-way repeater device 1306 is presented for use in a transmission device such as the transmission device 101 or 102 presented in connection with Fig. 1 . It should be noted that while the couplers are illustrated as stub couplers, any other couplers described herein including arc couplers, antenna or horn couplers, magnetic couplers, etc. may equally be used design. Bi-directional repeater 1306 may employ diversity paths where two or more wires or other transmission media exist. Such guided wave transmission has different transmission efficiencies and coupling efficiencies for different types of transmission media (such as insulated wires, uninsulated wires, or other types of transmission media), and further, if exposed to the elements, may be affected by Influenced by weather and other atmospheric conditions, it may be advantageous to selectively transmit over different transmission media at specific times. In various embodiments, various transmission media may be designated as primary, secondary, or tertiary, etc., regardless of whether such designation indicates preference for one transmission medium over another.

In the illustrated embodiment, transmission media includes insulated or uninsulated wire 1302 and insulated or uninsulated wire 1304 (referred to herein as wire 1302 and wire 1304, respectively). Repeater device 1306 receives guided waves traveling along wire 1302 using receiver coupler 1308 and relays the transmission as a guided wave along wire 1304 using transmitter waveguide 1310 . In other embodiments, repeater device 1306 may switch from wire 1304 to wire 1302, or may relay transmissions along the same path. Repeater device 1306 may include a sensor, or be in communication with a sensor (or network management system 1601 as depicted in FIG. 16A ) that indicates a condition that may affect transmission. Based on the feedback received from the sensors, the repeater device 1306 may determine whether to maintain the transmission along the same wire or divert the transmission to another wire.

Turning now to FIG. 14 , illustrated is a block diagram 1400 illustrating an example, non-limiting embodiment of a two-way repeater system. In particular, a two-way repeater system for use in a transmission device such as the transmission device 101 or 102 presented in connection with Fig. 1 is presented. The two-way repeater system includes waveguide coupling devices 1402 and 1404 that receive and transmit transmissions from other coupling devices located in the distributed antenna system or backhaul system.

In various embodiments, waveguide coupling device 1402 may receive a transmission from another waveguide coupling device, wherein the transmission has multiple subcarriers. A duplexer 1406 may separate the transmission from other transmissions and direct the transmission to a low noise amplifier (“LNA”) 1408 . With the help of the local oscillator 1412, the mixer 1428 can down-convert the transmission (which in some embodiments is within the mmWave band or around 38 GHz) to a lower frequency, such as the cellular band for distributed antenna systems ( approximately 1.9 GHz), the natural frequency, or other frequencies for backhaul systems. Extractor (or demultiplexer) 1432 may extract the signal on the subcarriers and direct the signal to output section 1422 for optional amplification, buffering, or isolation by power amplifier 1424 for coupling to communication interface 205 . Communication interface 205 may further process signals received from power amplifier 1424 or otherwise transmit such signals to other devices, such as base stations, mobile devices, buildings, etc., through a wireless or wired interface. For signals not extracted at this location, the extractor 1432 may redirect them to another mixer 1436 where they are used to modulate a carrier generated by the local oscillator 1414 . Using its subcarriers, the carrier is directed to a power amplifier ("PA") 1416 and retransmitted by waveguide coupling device 1404 via duplexer 1420 to another system.

The LNA 1426 may be used to amplify, buffer or isolate signals received by the communication interface 205 before sending the signals to the multiplexer 1434, which combines the signals with those already coupled from the waveguide The signals received by device 1404 are combined. The signal received from coupling device 1404 has been split by duplexer 1420 , then passed through LNA 1418 , and down-converted by mixer 1438 . When the signals are combined by the multiplexer 1434, the signals are up-converted by the mixer 1430, then boosted by the PA 1410, and passed on to another system through the waveguide coupling device 1402. In an embodiment, the two-way repeater system may simply be a repeater without the output device 1422 . In this embodiment, multiplexer 1434 would not be used, and the signal from LNA 1418 would be directed to mixer 1430 as previously described. It should be appreciated that in some embodiments, a two-way repeater system may also be implemented using two distinct and separate one-way repeaters. In alternative embodiments, the two-way repeater system may also be a booster or otherwise perform retransmissions without downscaling and upscaling. Indeed, in example embodiments, the retransmission may be based on receiving the signal or guided wave and performing some signal or guided wave processing or reshaping, filtering and/or amplifying prior to retransmission of the signal or guided wave.

Referring now to FIG. 15 , there is shown a block diagram 1500 illustrating an example non-limiting embodiment of a guided wave communication system. This diagram depicts an exemplary embodiment in which a guided wave communication system such as that presented in connection with FIG. 1 may be used.

In order to provide network connectivity to additional base station equipment, the backhaul network of network equipment linking communication cells (eg micro cells and macro cells) to the core network expands accordingly. Similarly, in order to provide network connectivity to distributed antenna systems, an extended communication system linking base station equipment and its distributed antennas is desirable. A guided wave communication system 1500 such as that shown in FIG. ) communications, such as a transmission medium such as a wire that operates as a single-conductor transmission line (eg, a utility line) and that may act as a waveguide and/or otherwise operate to guide the transmission of electromagnetic waves.

Guided wave communication system 1500 can include a first instance 1550 of a distribution system comprising one or more base station devices (eg, base station device 1504 ) communicatively coupled to central office 1501 and/or macrocell site 1502 . Base station equipment 1504 may be connected to macrocell site 1502 and central office 1501 by wired (eg, optical fiber and/or cable) or by wireless (eg, microwave wireless) connections. A second instance 1560 of a distribution system can be used to provide wireless voice and data services to mobile devices 1522 and to residential and/or commercial establishments 1542 (referred to herein as establishments 1542). System 1500 may have additional instances 1550 and 1560 of distribution systems for providing voice and/or data services to mobile devices 1522-1524 and institution 1542 as shown in FIG. 15 .

A macro cell, such as macro cell site 1502, may have a dedicated connection to the mobile network and base station equipment 1504, or may share and/or otherwise use another connection. Central office 1501 may be used to distribute media content and/or provide Internet service provider (ISP) services to mobile devices 1522-1524 and institution 1542. Central office 1501 may receive media content or other content sources from satellite constellation 1530 (one of which is shown in FIG. 15 ) and distribute such content to mobile Devices 1522-1524 and mechanism 1542. Central office 1501 may also be communicatively coupled to Internet 1503 for providing Internet data services to mobile devices 1522-1524 and institution 1542.

Base station equipment 1504 may be mounted on or attached to a utility pole 1516 . In other embodiments, base station equipment 1504 may be near a transformer and/or near other locations located near power lines. Base station equipment 1504 can facilitate connection of mobile devices 1522 and 1524 to a mobile network. Antennas 1512 and 1514 mounted on or near utility poles 1518 and 1520, respectively, can receive signals from base station equipment 1504 and transmit those signals over a much wider area than if antennas 1512 and 1514 were located at or near base station equipment 1504 to mobile devices 1522 and 1524.

It should be noted that, for simplicity, Figure 15 shows three utility poles, with one base station device, in each instance 1550 and 1560 of the distribution system. In other embodiments, utility pole 1516 may have more base station equipment, and more utility poles with distributed antennas and/or tethered connections to agency 1542 .

Transmission device 1506 (such as transmission device 101 or 102 given in connection with FIG. 1512 and 1514. To transmit the signal, the wireless power supply and/or transmission device 1506 upconverts (e.g., via frequency mixing) or otherwise frequency converts the signal from the base station device 1504 to a microwave band signal, and the transmission device 1506 transmits Microwave band waves propagating as guided waves traveling along utility lines or other conductors as described in the previous embodiments. At the utility pole 1518, another transmission device 1508 receives the guided waves (and may optionally amplify them as needed or desired or operate as a repeater to receive and regenerate the guided waves) and Send it forward on utility lines or other conductors as guided waves. The transmission device 1508 may also extract the signal from the microwave band guided wave and shift down or otherwise frequency convert it to its native cellular band frequency (e.g., 1.9 GHz or other defined cellular frequency) or another cellular ( or non-cellular) band frequencies. Antenna 1512 may wirelessly transmit the down-converted signal to mobile device 1522 . The process may be repeated by transmitting device 1510, antenna 1514, and mobile device 1524 as needed or desired.

Transmissions from mobile devices 1522 and 1524 may also be received by antennas 1512 and 1514, respectively. Transmission devices 1508 and 1510 may upconvert or otherwise convert cellular frequency band signals to the microwave frequency band and transmit the signals as guided waves (e.g., surface waves or other electromagnetic waves) over the power line(s) to base station equipment 1504 .

Media content received by central office 1501 may be supplied via base station equipment 1504 to a second instance of distribution system 1560 for distribution to mobile devices 1522 and institutions 1542 . Transmission device 1510 may be tethered to institution 1542 via one or more wired connections or a wireless interface. The one or more wired connections may include, but are not limited to, power lines, coaxial cables, fiber optic cables, twisted pair cables, guided wave transmission media, or other means for distributing media content and/or for providing Internet services suitable wired medium. In an example embodiment, the wired connection from the transmission device 1510 may be communicatively coupled to one or more very high bit rate digital A Subscriber Line (VDSL) modem, each SAI or pedestal provides service to a portion of the facility 1542. A VDSL modem may be used to selectively distribute media content and/or provide Internet services to a gateway (not shown) located in establishment 1542. The SAI or pedestal may also be communicatively coupled to mechanism 1542 via a wired medium such as power lines, coaxial cables, fiber optic cables, twisted pair cables, guided wave transmission media, or other suitable wired medium. In other example embodiments, the transport device 1510 may be directly communicatively coupled to the mechanism 1542 without an intermediate interface, such as an SAI or a pedestal.

In another example embodiment, system 1500 may employ a diversity path in which two or more utility lines or other conductors are connected in series between poles 1516, 1518, and 1520 (e.g., between pole 1516 and power line two or more conductors between poles 1520), and redundant transmissions from base station/macrocell site 1502 are transmitted as guided waves beneath the surface of utility lines or other conductors. The utility lines or other wires may be insulated or uninsulated, and depending on the environmental conditions causing the transmission loss, the coupling device may selectively receive signals from insulated or uninsulated utility lines or other wires. The selection may be based on measurements of the signal-to-noise ratio of the wire or on determined weather/environmental conditions (eg, humidity detectors, weather forecast, etc.). Using diversity paths with system 1500 can enable alternate routing capabilities, load balancing, increased load handling, concurrent bi-directional or synchronous communications, spread spectrum communications, and the like.

It should be noted that the use of transmission devices 1506, 1508, and 1510 in Figure 15 is exemplary only, and that other uses are possible in other embodiments. For example, transmission equipment may be used in a backhaul communication system to provide network connectivity to base station equipment. Transmission devices 1506, 1508, and 1510 may be used in many situations where it is desired to transmit guided wave communications over wires (whether insulated or uninsulated). Transmission devices 1506, 1508, and 1510 are improvements over other coupling devices by having no or limited physical and/or electrical contact with wires that can carry high voltages. The transmission device may be located away from (eg, spaced from) the wire and/or on the wire as long as it is not in electrical contact with the wire, since the dielectric acts as an insulator, thereby allowing cheap, easy and/or less complicated installation. However, as previously mentioned, conductive couplers or non-dielectric couplers may be used, for example, in configurations where the wires correspond to telephone networks, cable television networks, broadband data services, fiber optic communication systems, or other networks using low voltage or having insulated transmission lines middle.

It should also be noted that although base station equipment 1504 and macrocell sites 1502 are shown in the embodiments, other network configurations are equally possible. For example, devices such as access points or other wireless gateways can be used in a similar manner to extend other networks (such as wireless local area networks, wireless personal area other wireless networks that operate on the communication protocol of the wireless protocol).

Referring now to FIGS. 16A and 16B , block diagrams illustrating an example non-limiting embodiment of a system for managing a grid communication system are shown. Considering FIG. 16A , there is shown a waveguide system 1602 for use in a guided wave communication system such as that presented in connection with FIG. 15 . The waveguide system 1602 may include a sensor 1604 , a power management system 1605 , a transmission device 101 or 102 including at least one communication interface 205 , a transceiver 210 and a coupler 220 .

Waveguide system 1602 may be coupled to power line 1610 for facilitating guided wave communications according to embodiments described in the subject disclosure. In an example embodiment, the transmission device 101 or 102 includes a coupler 220 for inducing electromagnetic waves propagating longitudinally along the surface of the power line 1610 on the surface of the power line 1610 as described in the subject disclosure . The transmission device 101 or 102 may also act as a repeater as shown in FIGS. .

The transmission device 101 or 102 comprises a transceiver 210 configured for up-converting, for example, a signal operating on an original frequency range to electromagnetic waves operating at, exhibiting or associated with a carrier frequency, said The electromagnetic waves propagate along the couplers for inducing corresponding guided electromagnetic waves that propagate along the surface of the power line 1610 . The carrier frequency may be represented by a center frequency having an upper limit cutoff frequency and a lower limit cutoff frequency defining the electromagnetic wave bandwidth. Power line 1610 may be a wire (eg, single or multiple strands) having a conductive surface or an insulating surface. Transceiver 210 may also receive signals from coupler 220 and down-convert electromagnetic waves operating at a carrier frequency to a signal at its original frequency.

The signals for up-conversion received by the communication interface 205 of the transmission device 101 or 102 may include, but are not limited to: by the central office 1611 on the wired or wireless interface of the communication interface 205, by the base station 1614 on the wired or wireless interface of the communication interface 205 Signals supplied on the wireless interface; signals transmitted by the mobile device 1620 to the base station 1614 for communication on the wired or wireless interface of the communication interface 205; supplied by the in-building communication device 1618 on the wired or wireless interface of the communication interface 205 and/or wireless signals supplied to the communication interface 205 by the mobile device 1612 roaming within the wireless communication range of the communication interface 205. In embodiments where waveguide system 1602 is used as a repeater such as shown in FIGS. 12-13 , communication interface 205 may or may not be included in waveguide system 1602 .

Electromagnetic waves propagating along the surface of power line 1610 may be modulated and formatted to include data packets or data frames that include data payloads and further include networking information (such as identifying one or more header information for the destination waveguide system 1602). The networking information may be provided by waveguide system 1602 or an originating device such as central office 1611, base station 1614, mobile device 1620, or in-building device 1618, or a combination thereof. Additionally, the modulated electromagnetic waves may include error correction data for mitigating signal disturbances. The networking information and error correction data may be used by destination waveguide system 1602 to detect transmissions directed thereto and to downconvert and process transmissions with error correction data, including those directed to The ground waveguide system 1602 receives voice signals and/or data signals from the communication device.

Referring now to sensor 1604 of waveguide system 1602, sensor 1604 may include one or more of: temperature sensor 1604a, disturbance detection sensor 1604b, energy loss sensor 1604c, noise sensor 1604d, vibration sensor 1604e, environment (e.g., weather) sensor 1604f, and/or image sensor 1604g. Temperature sensor 1604a may be used to measure ambient temperature, temperature of transmission device 101 or 102, temperature of power line 1610, temperature differences (e.g., compared to a set point or baseline, between transmission device 101 or 102 and 1610, etc. ), or any combination thereof. In one embodiment, the temperature measurement can be periodically collected by the base station 1614 and reported to the network management system 1601 .

The disturbance detection sensor 1604b may perform measurements on the power line 1610 to detect disturbances, such as signal reflections, which may indicate the presence of downstream disturbances that may impede the propagation of electromagnetic waves on the power line 1610 . Signal reflections may represent distortions due to, for example, electromagnetic waves transmitted on the power line 1610 by the transmission device 101 or 102 , which are reflected in whole or in part from disturbances in the power line 1610 downstream of the transmission device 101 or 102 back to the transmission device 101 or 102 .

Signal reflections may be caused by obstructions on the power line 1610 . For example, tree branches can cause electromagnetic wave reflections when they are on or very close to power line 1610 (which can cause corona discharge). Other obstacles that may cause electromagnetic wave reflections may include, but are not limited to: objects that have become wrapped around the power line 1610 (e.g., clothing, shoes wrapped around the power line 1610 with shoelaces, etc.), corrosion buildup on the power line 1610 or ice buildup. Grid components may also impede and impede the propagation of electromagnetic waves on the surface of the power line 1610 . Illustrations of grid components that can cause signal reflections include, but are not limited to, transformers and splices used to connect spliced power lines. Sharp angles on the power line 1610 can also cause electromagnetic wave reflections.

Disturbance detection sensor 1604b may include circuitry for comparing the magnitude of the reflected electromagnetic wave with the magnitude of the original electromagnetic wave transmitted by transmission device 101 or 102 to determine how much transmission is attenuated by downstream disturbances in power line 1610 . The disturbance detection sensor 1604b may further include a spectrum analyzer circuit for spectrally analyzing the reflected waves. Spectral data generated by the spectrum analyzer circuit may be compared to spectral distribution curves via pattern recognition, expert systems, curve fitting, matched filtering, or other artificial intelligence, classification, or comparison techniques to base, for example, the spectral data that most closely matches the spectral data Distribution curves to identify the type of perturbation. The spectral profile may be stored in the memory of the disturbance detection sensor 1604b, or may be accessed remotely by the disturbance detection sensor 1604b. The profile may include spectral data that models different disturbances that may be encountered on the power line 1610 in order to enable the disturbance detection sensor 1604b to locally identify disturbances. The identity of the disturbance (if known) can be reported to the network management system 1601 through the base station 1614 . The disturbance detection sensor 1604b can also utilize the transmission device 101 or 102 to transmit electromagnetic waves as a test signal in order to determine the round-trip time of the electromagnetic wave reflection. The round-trip time measured by the disturbance detection sensor 1604b can be used to calculate the distance traveled by the electromagnetic wave until the point at which the reflection occurs, which enables the disturbance detection sensor 1604b to calculate the distance from the transmission device 101 or 102 to a downstream disturbance on the power line 1610.

The calculated distance may be reported to the network management system 1601 through the base station 1614 . In one embodiment, the location of the waveguide system 1602 on the power line 1610 may be known to the network management system 1601, which may use the location to determine the location on the power line 1610 based on the known topology of the power grid. the location of the disturbance. In another embodiment, the waveguide system 1602 may provide its location to the network management system 1601 to assist in determining the location of a disturbance on the power line 1610 . The position of the waveguide system 1602 may be obtained by the waveguide system 1602 from a pre-programmed position of the waveguide system 1602 stored in the memory of the waveguide system 1602, or the waveguide system 1602 may use a GPS receiver (not shown) included in the waveguide system 1602. ) to determine its location.

The power management system 1605 provides power to the aforementioned components of the waveguide system 1602 . Power management system 1605 may receive power from a solar cell, or from a transformer (not shown) coupled to power line 1610, or by inductive coupling to power line 1610 or another nearby power line. The power management system 1605 may also include battery backup and/or supercapacitors or other capacitor circuits for providing temporary power to the waveguide system 1602 . The energy loss sensor 1604c may be used to detect when the waveguide system 1602 has a loss of power condition and/or the occurrence of some other fault. For example, the energy loss sensor 1604c may detect when there is a loss of power due to a defective solar cell, an obstruction on the solar cell causing it to fail due to a loss of power on the power line 1610, and/or when the backup power system is failure of the supercapacitor, a detectable defect in the supercapacitor. The energy loss sensor 1604c may notify the network management system 1601 via the base station 1614 when a failure and/or power loss occurs.

Noise sensor 1604d may be used to measure noise on power line 1610 that may adversely affect the transmission of electromagnetic waves on power line 1610 . Noise sensor 1604d may sense undesired electromagnetic interference, noise bursts, or other disturbance sources that may interrupt reception of modulated electromagnetic waves on the surface of power line 1610 . Noise bursts may be caused by, for example, corona discharge or other noise sources. The noise sensor 1604d can compare the measured noise with the measured noise by the waveguide system 1602 via pattern recognition, expert system, curve fitting, matched filtering, or other artificial intelligence, classification, or comparison techniques from an internal noise profile database or from a remotely located database storing noise profiles. The obtained noise curves are compared. By comparison, the noise sensor 1604d may identify a noise source (eg, corona discharge or otherwise) based, for example, on the noise profile that provides the closest match to the measured noise. Noise sensor 1604d may also detect how noise affects transmissions by measuring transmission metrics such as bit error rate, packet loss rate, jitter, packet retransmission requests, and the like. The noise sensor 1604d may report to the network management system 1601 the identity of the noise source, its occurrence time, and transmission metrics through the base station 1614 .

Vibration sensors 1604e may include accelerometers and/or gyroscopes for detecting 2D or 3D vibrations on power line 1610 . The vibrations can be compared via pattern recognition, expert systems, curve fitting, matched filtering, or other artificial intelligence, classification, or comparison techniques to vibration profiles that can be stored locally in the waveguide system 1602 or obtained by the waveguide system 1602 from a remote database Compare. The vibration profile may eg be used to distinguish a fallen tree from a gust of wind based eg on the vibration profile providing the closest match to the measured vibrations. The result of this analysis can be reported to the network management system 1601 by the vibration sensor 1604e through the base station 1614 .

Environmental sensors 1604f may include barometers for measuring barometric pressure, ambient temperature (which may be provided by temperature sensor 1604a), wind speed, humidity, wind direction, rainfall, and the like. Environmental sensors 1604f may collect raw information and combine it with memory or remote This information is processed by comparing environmental distribution curves obtained with the database to predict weather conditions before they occur. The environmental sensor 1604f can report the raw data and its analysis to the network management system 1601 .

Image sensor 1604g may be a digital camera (eg, charge-coupled device or CCD imager, infrared camera, etc.) for capturing images of the vicinity of waveguide system 1602 . Image sensor 1604g may include an electromechanical mechanism to control movement (e.g., actual position or focus/zoom) of a camera used to inspect power line 1610 from multiple viewing angles (e.g., top surface, bottom surface, left surface, right surface, etc.) . Alternatively, image sensor 1604g may be designed such that no electromechanical mechanism is required to obtain the multiple viewing angles. The collection and retrieval of imaging data generated by the image sensor 1604g may be controlled by the network management system 1601 , or may be collected and reported to the network management system 1601 by the image sensor 1604g autonomously.

Telemetry information applicable to collecting telemetry information associated with the waveguide system 1602 and/or the power line 1610 may be used by the waveguide system 1602 for use in detecting, predicting, and/or mitigating electromagnetic waves that may impede transmission of electromagnetic waves on the power line 1610 (or any other form) Other sensors for disturbances propagated on transmission media).

Referring now to FIG. 16B , a block diagram 1650 illustrates an example, non-limiting embodiment of a system for managing a power grid 1653 and a communication system 1655 embedded therein or associated therewith, in accordance with various aspects described herein. Communication system 1655 includes multiple waveguide systems 1602 coupled to power lines 1610 of grid 1653 . At least a portion of waveguide system 1602 used in communication system 1655 may communicate directly with base station 1614 and/or network management system 1601 . A waveguide system 1602 not directly connected to the base station 1614 or the network management system 1601 may conduct a communication session with the base station 1614 or the network management system 1601 through other downstream waveguide systems 1602 connected to the base station 1614 or the network management system 1601 .

Network management system 1601 may be communicatively coupled to equipment of utility company 1652 and equipment of communication service provider 1654 to provide each entity with status information associated with grid 1653 and communication system 1655, respectively. Network management system 1601, utility company 1652 equipment, and communication service provider 1654 may access communication equipment used by utility company personnel 1656 and/or communication equipment used by communication service provider personnel 1658 for providing Status information and/or used to guide such personnel in managing the grid 1653 and/or communication system 1655.

Figure 17A illustrates a flowchart of an example non-limiting embodiment of a method 1700 for detecting and mitigating disturbances occurring in the communication network of the systems of Figures 16A and 16B. Method 1700 may begin at step 1702 in which waveguide system 1602 transmits and receives messages embedded in modulated electromagnetic waves or another type of electromagnetic wave traveling along the surface of power line 1610, or forming the A portion of a modulated electromagnetic wave or another type of electromagnetic wave. The messages may be voice messages, streaming video, and/or other data/information exchanged between communication devices communicatively coupled to the communication system 1655 . At step 1704, sensor 1604 of waveguide system 1602 may acquire sensing data. In an embodiment, sensory data may be collected in step 1704 before, during or after transmitting and/or receiving a message in step 1702 . At step 1706, waveguide system 1602 (or sensor 1604 itself) may determine from the sensed data the actual or predicted occurrence of a disturbance in communication system 1655 that may affect ) or communications received by the waveguide system. The waveguide system 1602 (or sensor 1604) may process temperature data, signal reflection data, energy loss data, noise data, vibration data, environmental data, or any combination thereof to make this determination. Waveguide system 1602 (or sensor 1604 ) may also detect, identify, estimate, or predict sources of disturbance and/or their location in communication system 1655 . If a disturbance is neither detected/identified nor predicted/estimated in step 1708, the waveguide system 1602 may proceed to step 1702 where it continues to transmit and receive messages embedded along the power line 1610 in, or form part of, a modulated electromagnetic wave traveling on the surface of the

If at step 1708 a disturbance is detected/identified or predicted/estimated to occur, the waveguide system 1602 proceeds to step 1710 to determine whether the disturbance adversely affected the transmission or reception of the message in the communication system 1655 (or alternatively, possible adverse effects or the extent of their possible adverse effects). In one embodiment, the duration threshold and the frequency of occurrence threshold may be used at step 1710 to determine when a disturbance adversely affects communications in the communication system 1655 . For purposes of illustration only, assume that the duration threshold is set at 500 ms, while the frequency of occurrence threshold is set at 5 disturbances within a 10 second observation period. Therefore, a disturbance with a duration greater than 500ms will trigger the duration threshold. Additionally, any perturbation that occurs more than 5 times within a 10 second time interval will trigger the occurrence frequency threshold.

In one embodiment, a disturbance may be considered to adversely affect signal integrity in the communication system 1655 when only a duration threshold is exceeded. In another embodiment, a disturbance may be considered to adversely affect signal integrity in the communication system 1655 when both a duration threshold and a frequency of occurrence threshold are exceeded. Thus, the latter embodiment is more conservative than the former embodiment in terms of classifying disturbances that adversely affect signal integrity in the communication system 1655 . It will be appreciated that many other algorithms and associated parameters and thresholds may be used for step 1710 according to example embodiments.

Referring back to method 1700, if at step 1710, the disturbance detected at step 1708 does not meet the criteria for adversely affected communications (e.g., neither exceeds a duration threshold nor exceeds a frequency of occurrence threshold), then waveguide system 1602 may Proceed to step 1702 and continue processing messages. For example, if the disturbance detected in step 1708 has a duration of 1 millisecond, with a single occurrence within a period of 10 seconds, then neither of these two thresholds will be exceeded. Accordingly, such disturbances may be considered to have negligible impact on signal integrity in the communication system 1655 and thus will not be flagged as disturbances requiring mitigation. Although not flagged, disturbance occurrences, time of their occurrence, frequency of their occurrence, spectral data, and/or other useful information may be reported as telemetry data to the network management system 1601 for monitoring purposes.

Referring back to step 1710, if on the other hand the disturbance satisfies the criteria for adversely affected communications (e.g., exceeds either or both of these two thresholds), then the waveguide system 1602 may proceed to step 1712 and send the event Report to the network management system 1601. The report may include raw sensed data collected by the sensors 1604, a description of the disturbance by the waveguide system 1602 (if known), when the disturbance occurred, how often the disturbance occurred, the location associated with the disturbance, parameter readings such as bit errors rate, packet loss rate, retransmission request, jitter, delay time, etc.). The report may include the expected disturbance type if the disturbance is based on predictions made by one or more sensors of the waveguide system 1602, and if predictable, when the prediction is based on historical sensing collected by the sensors 1604 of the waveguide system 1602 When using data, the report may include an expected time of occurrence of the disturbance, and a predicted expected frequency of occurrence of the disturbance.

At step 1714, the network management system 1601 may determine mitigation, avoidance, or corrective techniques, which may include directing the waveguide system 1602 to reroute traffic to avoid the disturbance if the location of the disturbance can be determined. In one embodiment, a waveguide coupling device 1402 that detects a disturbance may direct a repeater, such as the one shown in FIGS. Power lines are required to enable the waveguide system 1602 to reroute traffic to a different transmission medium and avoid disturbances. In embodiments where the waveguide system 1602 is configured as a repeater, the waveguide system 1602 may itself reroute traffic from the primary power line to the secondary power line. It should be further noted that for two-way communication (e.g., full-duplex communication or half-duplex communication), repeaters may be configured to reroute traffic from the secondary power line back to the primary power line for the waveguide system 1602 for processing.

In another embodiment, the waveguide system 1602 may redirect traffic by instructing a first repeater located upstream of the disturbance and a second repeater located downstream of the disturbance to redirect traffic from the main repeater in a manner that avoids the disturbance. Power lines are temporarily redirected to secondary power lines and redirected back to primary power lines. It should be further noted that for bi-directional communication (eg, full-duplex communication or half-duplex communication), repeaters may be configured to reroute traffic from the secondary power line back to the primary power line.

To avoid interrupting existing communication sessions taking place on the secondary power line, the network management system 1601 may direct the waveguide system 1602 to instruct the repeater(s) to use the unused time slot(s) of the secondary power line and/or ( multiple) frequency bands to redirect data and/or voice traffic away from main power lines to avoid disturbances.

At step 1716, the network management system 1601 may notify the equipment of the utility company 1652 and/or the equipment of the communication service provider 1654 when the traffic is being rerouted to avoid the disturbance, which in turn may notify the utility company's personnel 1656 and/or communication service provider personnel 1658 to notify of the detected disturbance and its location, if known. Field personnel from either party can work to resolve the disturbance at the determined disturbance location. Once the disturbance has been removed or otherwise mitigated by utility company personnel and/or communications service provider personnel, those personnel can use on-site equipment communicatively coupled to network management system 1601 (e.g., laptops, smart phone, etc.), and/or utility company and/or communication service provider equipment to notify its corresponding company and/or network management system 1601. The notification may include a description of how to mitigate the disturbance, as well as any changes to the power line 1610 that may change the topology of the communication system 1655 .

Once the disturbance has been resolved (as determined in decision 1718), network management system 1601 may direct waveguide system 1602 at step 1720 to restore the previous routing configuration used by waveguide system 1602, or if the recovery strategy used to mitigate the disturbance Traffic is routed according to the new routing configuration when a new network topology for the communication system 1655 is induced. In another embodiment, the waveguide system 1602 may be configured to monitor the mitigation of the disturbance by transmitting a test signal on the power line 1610 to determine when the disturbance has been removed. Once the waveguide system 1602 detects that there is no disturbance, if it determines that the network topology of the communication system 1655 has not changed, it can restore its routing configuration autonomously without the assistance of the network management system 1601, or it can use New routing configuration for new network topology.

Figure 17B illustrates a flowchart of an example non-limiting embodiment of a method 1750 for detecting and mitigating disturbances occurring in the communication network of the systems of Figures 16A and 16B. In one embodiment, method 1750 may begin with step 1752 in which network management system 1601 receives maintenance information associated with a maintenance schedule from utility company 1652 equipment or communication service provider 1654 equipment. The network management system 1601 may identify maintenance activities to be performed during the maintenance schedule from the maintenance information at step 1754 . Through these activities, the network management system 1601 can detect that due to maintenance (e.g., a scheduled replacement of the power line 1610, a scheduled replacement of the waveguide system 1602 on the power line 1610, a scheduled replacement of the power line 1610 in the grid 1653 configuration, etc.)

In another embodiment, network management system 1601 may receive telemetry information from one or more waveguide systems 1602 at step 1755 . The telemetry information may include, among other things: the identity of each waveguide system 1602 that submitted the telemetry information; measurements made by the sensors 1604 of each waveguide system 1602; Information related to disturbances, estimated disturbances or actual disturbances; location information associated with each waveguide system 1602; estimated locations of detected disturbances, identification of disturbances, etc. The network management system 1601 may use the telemetry information to determine the types of disturbances that may be detrimental to waveguide operation, electromagnetic wave transmission along the wire surface, or both. Network management system 1601 may also use telemetry information from multiple waveguide systems 1602 in order to isolate and identify disturbances. Additionally, the network management system 1601 may request telemetry information from waveguide systems 1602 in the vicinity of the affected waveguide system 1602 in order to triangulate the location of the disturbance and/or verify the identity of the disturbance by receiving similar telemetry information from other waveguide systems 1602 .

In yet another embodiment, the network management system 1601 may receive an unscheduled activity report from maintenance field personnel at step 1756 . Unscheduled maintenance may occur as a result of an unscheduled field call, or as a result of an unexpected field problem discovered during a field call or scheduled maintenance activity. The activity report may identify changes to the topological configuration of the grid 1653, changes to one or more waveguide systems 1602 (such as replacement or repair thereof), changes to the grid 1653 due to on-site personnel addressing issues discovered in the communication system 1655 and/or grid 1653, Performed disturbance mitigation (if any), etc.

At step 1758, the network management system 1601 may determine whether the disturbance will occur based on maintenance schedules, or determine whether the disturbance has occurred or is predicted to occur based on telemetry data, or determine whether the disturbance is due to Disturbances have occurred for unscheduled maintenance identified in the activity report. From any of these reports, the network management system 1601 can determine whether a detected or predicted disturbance requires rerouting of traffic by the affected waveguide system 1602 or other waveguide systems 1602 of the communication system 1655 .

When a disturbance is detected or predicted at step 1758, then the network management system 1601 may proceed to step 1760 where the network management system may direct one or more waveguide systems 1602 to reroute traffic to Avoid disturbances. When the disturbance is permanent due to a permanent topology change of the grid 1653 , the network management system 1601 may proceed to step 1770 and bypass steps 1762 , 1764 , 1766 and 1772 . At step 1770, network management system 1601 may direct one or more waveguide systems 1602 to use a new routing configuration adapted to the new topology. However, when a disturbance has been detected via telemetry information supplied by one or more waveguide systems 1602, the network management system 1601 may notify the utility company's maintenance personnel 1656 or the communication service provider's maintenance personnel 1658 of the disturbance's location, disturbance type of personnel, if known, and relevant information that may assist such personnel in mitigating disturbances. When the disturbance is expected to be due to maintenance activity, the network management system 1601 may direct one or more waveguide systems 1602 to reconfigure the traffic routing at a given schedule (consistent with the maintenance schedule) to avoid being caused by the maintenance activity during the maintenance schedule. caused disturbances.

Returning to step 1760 and when it is complete, the process may continue with step 1762. At step 1762, the network management system 1601 may monitor when the disturbance(s) have been mitigated by field personnel. Mitigation of the disturbance may be detected at step 1762 by analyzing field reports submitted to the network management system 1601 by field personnel utilizing field equipment (e.g., laptop computers or handheld computers/devices) over a communication network (e.g., a cellular communication system) to the network management system 1601 . If the field personnel have reported that the disturbance has been alleviated, the network management system 1601 may proceed to step 1764 to determine whether a topology change is required to alleviate the disturbance based on the field report. Topology changes may include rerouting power lines 1610, reconfiguring waveguide system 1602 to utilize different power lines 1610, otherwise utilizing alternate links to bypass disturbances, and the like. If a topology change has occurred, the network management system 1601 may at step 1770 direct one or more waveguide systems 1602 to use a new routing configuration adapted to the new topology.

However, if the topology change has not been reported by field personnel, the network management system 1601 can proceed to step 1766, where the network management system can direct one or more waveguide systems 1602 to send a test signal to test for (multiple times) ) to detect perturbations in the routing configuration already in use. A test signal can be sent to the affected waveguide system 1602 in the vicinity of the disturbance. The test signal may be used to determine whether a signal disturbance (eg, electromagnetic wave reflection) is detected by any of the waveguide systems 1602 . If the test signal confirms that the previous routing configuration is no longer subject to the previously detected disturbance(s), the network management system 1601 may direct the affected waveguide system 1602 at step 1772 to restore the previous routing configuration. However, if the test signal analyzed by one or more waveguide coupling devices 1402 and reported to the network management system 1601 indicates the presence of a disturbance(s) or a new disturbance(s), then the network management system 1601 will proceed to step 1768 And report this information to on-site personnel so as to further solve on-site problems. In this case, the network management system 1601 may continue to monitor the mitigation of the disturbance(s) at step 1762 .

In the foregoing embodiments, the waveguide system 1602 may be configured to adapt to changes in the grid 1653 and/or mitigation of disturbances. That is, one or more affected waveguide systems 1602 may be configured to self-monitor mitigation of the disturbance and reconfigure traffic routing without instructions being sent thereto by the network management system 1601 . In this embodiment, the one or more waveguide systems 1602 that are self-configurable can inform the network management system 1601 of their routing choices, so that the network management system 1601 can maintain a macroscopic view of the communication topology of the communication system 1655 .

Although the corresponding methods are shown and described as a series of blocks in FIG. 17A and FIG. The blocks may occur in a different order and/or concurrently with other blocks than depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methodologies described below.

Turning now to FIG. 18A , a block diagram illustrating an example, non-limiting embodiment of a transmission medium 1800 for propagating guided electromagnetic waves is shown. In particular, a further example of the transmission medium 125 presented in connection with FIG. 1 is given. In an embodiment, transmission medium 1800 may include first dielectric material 1802 and second dielectric material 1804 disposed thereon. In an embodiment, the first dielectric material 1802 may include a dielectric core (referred to herein as the dielectric core 1802), and the second dielectric material 1804 may include a cladding or shell, such as a dielectric foam that wholly or partially surrounds the dielectric core. (referred to herein as dielectric foam 1804). In an embodiment, the dielectric core 1802 and the dielectric foam 1804 may be axially aligned with each other (although this is not required). In an embodiment, the combination of dielectric core 1802 and dielectric foam 1804 can flex or bend at least 45 degrees without damaging the dielectric core 1802 and dielectric foam 1804 materials. In an embodiment, the outer surface of the dielectric foam 1804 may be further surrounded in whole or in part by a third dielectric material 1806, which may act as an outer sheath (referred to herein as sheath 1806). Jacket 1806 may prevent exposure of dielectric core 1802 and dielectric foam 1804 to environments (eg, water, soil, etc.) that may adversely affect electromagnetic wave propagation.

Dielectric core 1802 may comprise, for example, a high density polyethylene material, a high density polyurethane material, or other suitable dielectric material(s). Dielectric foam 1804 may comprise, for example, a porous plastic material such as a foamed polyethylene material, or other suitable dielectric material(s). Sheath 1806 may comprise, for example, polyethylene material or equivalent. In an embodiment, the dielectric constant of the dielectric foam 1804 may be (or substantially) lower than the dielectric constant of the dielectric core 1802 . For example, the dielectric constant of dielectric core 1802 may be approximately 2.3, while the dielectric constant of dielectric foam 1804 may be approximately 1.15 (slightly higher than that of air).

Dielectric core 1802 may be used to receive signals in the form of electromagnetic waves from a launch pad or other coupling device described herein configured to transmit guided electromagnetic waves over transmission medium 1800 . In one embodiment, the transmission 1800 may be coupled to a hollow waveguide 1808 structured as, for example, a circular waveguide 1809, which may receive electromagnetic waves from a radiating device such as a stub antenna (not shown). The hollow waveguide 1808 in turn can induce guided electromagnetic waves in the dielectric core 1802 . In this configuration, guided electromagnetic waves are guided by or confined to the dielectric core 1802 and propagate longitudinally along the dielectric core 1802 . By adjusting the electronics of the launch pad, the operating frequency of the electromagnetic waves can be selected such that the field strength profile 1810 of the guided electromagnetic waves extends little (or not at all) outside the sheath 1806 .

By maintaining most, if not all, of the field strength of the guided electromagnetic wave within portions of the dielectric core 1802, dielectric foam 1804, and/or jacket 1806, the transmission medium 1800 can be used in harsh environments without Adversely affect the propagation of electromagnetic waves propagating therein. For example, transmission medium 1800 may be buried in soil with no (or little) adverse effect on guided electromagnetic waves propagating in transmission medium 1800 . Similarly, transmission medium 1800 may be exposed to water (eg, rained on or placed underwater) with no (or little) adverse effect on guided electromagnetic waves propagating in transmission medium 1800 . In an embodiment, the propagation loss of the guided electromagnetic wave in the foregoing embodiments may be 1 dB to 2 dB or more per meter at an operating frequency of 60 GHz. Depending on the operating frequency of the guided electromagnetic wave and/or the material used for the transmission medium 1800, other propagation losses may be possible. In addition, depending on the materials used to construct transmission medium 1800 , transmission medium 1800 may buckle laterally in some embodiments with no (or little) adverse effect on guided electromagnetic waves propagating through dielectric core 1802 and dielectric foam 1804 .

FIG. 18B depicts a different transmission medium 1820 than transmission medium 1800 of FIG. 18A , again providing a further example of transmission medium 125 given in connection with FIG. 1 . Transmission medium 1820 shows like reference numerals for like elements of transmission medium 1800 of FIG. 18A . In contrast to transmission medium 1800 , transmission medium 1820 includes a conductive core 1822 having an insulating layer 1823 wholly or partially surrounding conductive core 1822 . The combination of insulating layer 1823 and conductive core 1822 will be referred to herein as insulated conductor 1825 . In the illustration of FIG. 18B , insulating layer 1823 is covered in whole or in part by dielectric foam 1804 and jacket 1806 , which may be constructed of materials previously described. In an embodiment, insulating layer 1823 may comprise a dielectric material (such as polyethylene) that has a higher dielectric constant than dielectric foam 1804 (eg, 2.3 and 1.15, respectively). In an embodiment, the components of transmission medium 1820 may be coaxially aligned (although this is not required). In an embodiment, a hollow waveguide 1808 having a metal plate 1809 which may be spaced (although not required) from the insulating layer 1823 may be used to launch guided electromagnetic waves propagating substantially on the outer surface of the insulating layer 1823, however, again Other coupling devices as described herein may be employed. In an embodiment, the guided electromagnetic waves may be sufficiently guided or confined by the insulating layer 1823 so as to guide the electromagnetic waves longitudinally along the insulating layer 1823 . By adjusting the operating parameters of the launch pad, the operating frequency of the guided electromagnetic waves emitted by the hollow waveguide 1808 can generate an electric field strength profile 1824 such that the guided electromagnetic waves are substantially confined within the dielectric foam 1804, thereby preventing the guided electromagnetic waves from being exposed to adverse The ground affects the environment (eg, water, soil, etc.) in which the guided electromagnetic wave propagates through the transmission medium 1820 .

FIG. 18C depicts transmission medium 1830 different from transmission medium 1800 and transmission medium 1820 of FIGS. 18A and 18B , yet provides a further example of transmission medium 125 given in connection with FIG. 1 . Transmission medium 1830 shows like reference numerals for like elements of transmission medium 1800 and transmission medium 1820 of FIGS. 18A and 18B , respectively. In contrast to transmission media 1800 and 1820, transmission media 1830 includes bare (or uninsulated) conductors 1832 surrounded in whole or in part by dielectric foam 1804 and jacket 1806, which may be composed of previously described materials. In an embodiment, the components of transmission medium 1830 may be coaxially aligned (although this is not required). In an embodiment, a hollow waveguide 1808 having a metal plate 1809 coupled to a bare conductor 1832 may be used to emit guided electromagnetic waves propagating substantially on the outer surface of the bare conductor 1832, however, other coupling devices described herein may equally be employed . In an embodiment, the guided electromagnetic wave may be sufficiently guided or confined by the bare conductor 1832 so that the guided electromagnetic wave is guided longitudinally along the bare conductor 1832 . By adjusting the operating parameters of the launch pad, the operating frequency of the guided electromagnetic waves emitted by the hollow waveguide 1808 can generate an electric field strength profile 1834 such that the guided electromagnetic waves are substantially confined within the dielectric foam 1804, thereby preventing the guided electromagnetic waves from being exposed to adverse The ground affects the environment (eg, water, soil, etc.) in which electromagnetic waves propagate through the transmission medium 1830 .

It should be noted that hollow launch pad 1808 used with transmission medium 1800, transmission medium 1820, and transmission medium 1830 of FIGS. 18A, 18B, and 18C, respectively, may be replaced with other launch pads or coupling devices. Additionally, the propagation mode(s) of electromagnetic waves of any of the foregoing embodiments may be fundamental mode(s), non-fundamental (or asymmetric) mode(s), or a combination thereof.

18D is a block diagram illustrating an example, non-limiting embodiment of bundled transmission media 1836 in accordance with various aspects described herein. Bundled transmission medium 1836 may include a plurality of cables 1838 held in place by flexible sleeves 1839 . The plurality of cables 1838 may include multiple instances of cable 1800 of FIG. 18A , multiple instances of cable 1820 of FIG. 18B , multiple instances of cable 1830 of FIG. 18C , or any combination thereof. Sleeve 1839 may include a dielectric material that prevents soil, water, or other external material from contacting the plurality of cables 1838 . In embodiments, multiple transmitting stations (each utilizing transceivers similar to those depicted in FIG. 10A or other coupling devices described herein) may be adapted to selectively induce inductive Each guided electromagnetic wave transmits different data (eg, voice, video, message, content, etc.). In an embodiment, by adjusting the operating parameters of each transmitting station or other coupling device, the electric field strength profile of each guided electromagnetic wave can be completely or substantially confined within the layer of the corresponding cable 1838 so as to reduce crosstalk between the cables 1838 .

In the event that the electric field strength profile of each guided electromagnetic wave is not completely or substantially confined within the corresponding cable 1838, crosstalk of electromagnetic signals can occur between the cables 1838, such as through the two cables as depicted in FIG. 18E The associated signal plots are illustrated. The graph in Figure 18E shows that when a guided electromagnetic wave is induced on a first cable, the transmitted electric and magnetic fields of the first cable can induce a signal on the second cable, which creates crosstalk. Several mitigation options may be used to reduce crosstalk between cables 1838 of Figure 18D. In an embodiment, an absorbing material 1840 (such as carbon) that can absorb electromagnetic fields can be applied to the cable 1838 as shown in FIG. Crosstalk between. In another embodiment (not shown), carbon beads may be added to the gaps between cables 1838 to reduce crosstalk.

In yet another embodiment (not shown), the diameters of the cables 1838 can be configured differently to change the propagation velocity of the guided electromagnetic waves between the cables 1838 to reduce crosstalk between the cables 1838 . In an embodiment (not shown), each cable 1838 may be asymmetrically shaped (eg, elliptical) in order to direct the guided electromagnetic fields of each cable 1838 away from each other to reduce crosstalk. In an embodiment (not shown), filler material such as dielectric foam may be added between the cables 1838 to space the cables 1838 sufficiently to reduce crosstalk therebetween. In an embodiment (not shown), longitudinal carbon strips or swirls may be applied to the outer surface of the jacket 1806 of each cable 1838 in order to reduce the radiation of guided electromagnetic waves outside the jacket 1806 and thereby reduce the distance between the cables 1838. crosstalk. In yet another embodiment, each transmitting station may be configured to transmit guided electromagnetic waves having different frequencies, modulations, wave propagation modes (such as quadrature frequencies, modulations or modes) in order to reduce crosstalk between cables 1838 .

In yet another embodiment (not shown), multiple pairs of cables 1838 may be helically twisted to reduce crosstalk between the pairs and other cables 1838 proximate to the pairs. In some embodiments, some cables 1838 may be twisted while other cables 1838 are not twisted in order to reduce crosstalk between cables 1838 . Additionally, each twisted pair of cables 1838 may have a different spacing (eg, a different twist rate, such as twists per meter) to further reduce crosstalk between the pair and other cables 1838 proximate to the pair. In another embodiment (not shown), a launch pad or other coupling device may be configured to induce a guided electromagnetic wave in the cable 1838 with an electromagnetic field extending beyond the jacket 1806 into the gap between the cables in order to reduce crosstalk between cables 1838. Applicants believe that any of the foregoing embodiments for mitigating crosstalk between cables 1838 may be combined in order to further reduce crosstalk therebetween.

18G and 18H are block diagrams illustrating example non-limiting embodiments of transmission media with inner waveguides according to various aspects described herein. In an embodiment, transmission medium 1841 may include core 1842 . In one embodiment, the core 1842 may be a dielectric core 1842 (eg, polyethylene). In another embodiment, core 1842 may be an insulated or uninsulated conductor. The core 1842 may be surrounded by an outer shell 1844 or an insulating layer of the conductive core comprising a dielectric foam (eg, expanded polyethylene material) with a lower dielectric constant than the dielectric core. The difference in dielectric constant enables electromagnetic waves to be confined and guided by the core 1842 . Housing 1844 may be covered by housing sheath 1845 . Outer sheath 1845 may be made of a rigid material (eg, high density plastic) or a high tensile strength material (eg, synthetic fiber). In an embodiment, a housing sheath 1845 may be used to protect the housing 1844 and core 1842 from exposure to adverse environments (eg, water, moisture, soil, etc.). In an embodiment, outer sheath 1845 may be sufficiently rigid to separate the outer surface of core 1842 from the inner surface of outer sheath 1845 , creating a longitudinal gap between outer sheath 1854 and core 1842 . The longitudinal void may be filled with the dielectric foam of the housing 1844 .

Transmission medium 1841 may further include a plurality of outer loop conductors 1846 . Outer loop conductor 1846 may be a strand of conductive material braided around housing sheath 1845 to cover housing sheath 1845 in whole or in part. The outer loop conductor 1846 may function as a power line with a return electrical path for receiving power signals from a source (eg, transformer, generator, etc.) similar to embodiments described in the subject disclosure. In one embodiment, the outer ring conductor 1846 may be covered by a cable jacket 1847 to prevent the outer ring conductor 1846 from being exposed to water, soil, or other environmental elements. Cable jacket 1847 may be made of insulating material, such as polyethylene. The core 1842 may serve as a central waveguide for propagating electromagnetic waves. Hollow waveguide launch pads 1808, such as circular waveguides previously described, may be used to launch signals that induce electromagnetic waves guided by core 1842 in a manner similar to that described for the embodiments of FIGS. 18A, 18B, and 18C. Electromagnetic waves may be guided by core 1842 without utilizing the electrical return path of outer ring conductor 1846 or any other electrical return path. By adjusting the electronics of the launch pad 1808 , the frequency of operation of the electromagnetic waves can be selected such that the field strength profile of the guided electromagnetic waves extends little (or not at all) outside the housing sheath 1845 .

In another embodiment, the transmission medium 1843 may include a hollow core 1842' surrounded by an outer sheath 1845'. The outer sheath 1845' may have an inner conductive surface material or other surface material that enables the hollow core 1842' to act as a conduit for electromagnetic waves. The housing sheath 1845' may be at least partially covered with the outer ring conductor 1846 described earlier for conducting power signals. In an embodiment, a cable jacket 1847 may be disposed on an outer surface of the outer ring conductor 1846 to prevent the outer ring conductor 1846 from being exposed to water, soil, or other environmental elements. The waveguide launch pad 1808 may be used to launch electromagnetic waves guided by the hollow core 1842' and the conductive inner surface of the outer sheath 1845'. In an embodiment (not shown), hollow core 1842' may further comprise dielectric foam as described earlier.

Transmission medium 1841 may represent a multipurpose cable that conducts power on outer ring conductor 1846 with an electrical return path and provides communication services through an inner waveguide comprising a combination of core 1842 , outer shell 1844 , and outer jacket 1845 . The inner waveguide can be used to transmit or receive electromagnetic waves guided by the core 1842 (without utilizing an electrical return path). Similarly, transmission medium 1843 may represent a multipurpose cable utilizing an electrical return path to conduct power on outer ring conductor 1846 and provide communication through an inner waveguide comprising a combination hollow core 1842' and outer jacket 1845' Serve. The inner waveguide can be used to transmit or receive electromagnetic waves guided by the hollow core 1842' and outer sheath 1845' (without utilizing an electrical return path).

Applicants believe that the embodiment of FIGS. 18G-18H may be adapted for use with multiple inner waveguides surrounded by outer ring conductor 1846. The inner waveguide may be adapted to use the crosstalk mitigation techniques described above (eg, twisted pairs of waveguides, waveguides with different physical dimensions, use of polarizers within the housing, use of different wave modes, etc.).

For purposes of illustration only, transmission media 1800, 1820, 1830, 1836, 1841, and 1843 will be referred to herein as cable 1850, with the understanding that cable 1850 may represent one of the transmission media described in the subject disclosure. Any one, or a bundle of multiple instances thereof. For purposes of illustration only, dielectric core 1802, insulated conductor 1825, bare conductor 1832, core 1842, or hollow core 1842′ of transmission media 1800, 1820, 1830, 1836, 1841, and 1843 will be referred to herein as a transmission core, respectively. 1852, it is to be understood that cable 1850 may utilize dielectric core 1802, insulated conductor 1825, bare conductor 1832, core 1842, or hollow core 1842' of transmission media 1800, 1820, 1830, 1836, 1841, and/or 1843, respectively.

Turning now to FIGS. 181 and 18J , block diagrams illustrating example, non-limiting embodiments of connector configurations that may be used with cable 1850 are shown. In one embodiment, cable 1850 may be configured with either a female connection arrangement or a male connection arrangement, as depicted in Figure 18I. The male configuration on the right side of FIG. 18I can be achieved by peeling back the dielectric foam 1804 (and sheath 1806 if present) to expose a portion of the transmission core 1852 . The female configuration on the left side of Figure 18I can be achieved by removing a portion of the transmission core 1852 while maintaining the dielectric foam 1804 (and sheath 1806, if present). In embodiments where the delivery core 1852 is hollow as described with respect to FIG. 18H , the male portion of the delivery core 1852 may represent a hollow core with a rigid outer surface that can be slid into the female arrangement on the left side of FIG. 18I to Align the hollow cores together. It should be further noted that in the embodiment of FIGS. 18G-18H , outer ring conductor 1846 may be modified to connect the male and female portions of cable 1850 .

Based on the embodiments described above, these two cables 1850 with male and female connector arrangements can be mated together. A sleeve with an adhesive liner or shrink wrap material (not shown) may be applied to the joint area between the cables 1850 to maintain the joint in a fixed position and prevent exposure (e.g., to water, soil, etc. ). When the cables 1850 are mated, the transmission core 1852 of one cable will be in close proximity to the transmission core 1852 of the other cable. Guided electromagnetic waves propagating by means of any transmission core 1852 of cable 1850 traveling in either direction can span between disjoint transmission cores 1852 whether or not the transmission cores 1852 are in contact, whether or not the transmission cores 1852 are coaxially aligned , and/or whether there is a gap between the transmission cores 1852.

In another embodiment, a splice device 1860 having a female connector arrangement at both ends may be used to mate with a cable 1850 having a male connector arrangement, as shown in Figure 18J. In an alternate embodiment, not shown in FIG. 18J , splicing device 1860 may be adapted to have male connector arrangements at both ends that may mate with cables 1850 having female connector arrangements. In another embodiment not shown in FIG. 18J , the splicing device 1860 can be adapted to have a male connector arrangement and a female connector arrangement at opposite ends, which can be combined with a female connector arrangement and a male connector arrangement, respectively. Arrange the cable 1850 to fit. It should be further noted that for a transmission core 1852 having a hollow core, the male and female arrangements described in FIG. 18I can be applied to the splicing device 1860 regardless of whether both ends of the splicing device 1860 are male and both are female. , or its combination.

The foregoing embodiments for connecting cables illustrated in FIGS. 181-18J may be applied to each individual instance of cables 1838 of bundled transmission medium 1836 . Similarly, the foregoing embodiments illustrated in FIGS. 18I to 18J may be applied to each individual instance of an inner waveguide of a cable 1841 or 1843 having multiple inner waveguides.

Turning now to FIG. 18K, there is shown a block diagram illustrating an example non-limiting embodiment of transmission media 1800', 1800", 1800"', and 1800"" for propagating guided electromagnetic waves. In an embodiment, the transmission medium 1800' may include a core 1801 and a dielectric foam 1804' divided into segments and covered by a jacket 1806, as shown in Figure 18K. Core 1801 may be represented by dielectric core 1802 of Figure 18A, insulated conductor 1825 of Figure 18B, or bare conductor 1832 of Figure 18C. Each section of dielectric foam 1804' may be separated by a void (eg, air, gas, vacuum, or a substance with a low dielectric constant). In an embodiment, as shown in FIG. 18K , the interstitial spacing between segments of the dielectric foam 1804' may be quasi-random, which may help reduce the gap between the dielectric foam 1804' as electromagnetic waves propagate longitudinally along the core 1801. The reflection of electromagnetic waves that occurs at each segment of the . Sections of dielectric foam 1804' may be configured, for example, as gaskets made of dielectric foam with internal openings for supporting core 1801 in a fixed position. For purposes of illustration only, the gasket will be referred to herein as gasket 1804'. In an embodiment, the interior opening of each gasket 1804 ′ may be coaxially aligned with the axis of the core 1801 . In another embodiment, the inner opening of each gasket 1804' may be offset from the axis of the core 1801 . In another embodiment (not shown), each gasket 1804' may have a variable longitudinal thickness, as shown by the difference in thickness of the gaskets 1804'.

In an alternative embodiment, the transmission medium 1800" may comprise a core 1801, and a strip of dielectric foam 1804" helically wound around the core, covered by a sheath 1806, as shown in Figure 18K. Although it may not be apparent from the diagram shown in FIG. 18K , in an embodiment, the strip of dielectric foam 1804" may be spaced at variable intervals (i.e., different rates of twist) around the core for different sections of the strip of dielectric foam 1804". 1801 twisted. Utilizing variable spacing can help reduce reflections or other interference of electromagnetic waves that occur between areas of the core 1801 that are not covered by the strips of dielectric foam 1804". It should be further noted that the thickness (diameter) of the strips of dielectric foam 1804" can be greater than The core 1801 shown in Figure 18K has a much larger diameter (eg, 2 or more times larger).

In an alternative embodiment, transmission medium 1800"' (shown in cross-sectional view) may include a non-circular core 1801' covered by dielectric foam 1804 and jacket 1806. In an embodiment, non-circular core 1801' may have an oval configuration as shown in Figure 18K or other suitable non-circular configurations. In another embodiment, the non-circular core 1801' may have an asymmetric configuration. Field polarization of electromagnetic waves induced on the non-circular core 1801'. The structure of the non-circular core 1801' can help maintain the polarization of the electromagnetic waves as they propagate along the non-circular core 1801'.

In an alternative embodiment, transmission medium 1800"" (shown in cross-sectional view) may include multiple cores 1801" (only two shown, but more are possible). The multiple cores 1801 ” may be covered by dielectric foam 1804 and sheath 1806. The plurality of cores 1801" may be used to polarize a field of electromagnetic waves induced on the plurality of cores 1801". The structure of the plurality of cores 1801" may maintain the polarization of the guided electromagnetic wave as it propagates along the plurality of cores 1801".

It should be appreciated that the embodiment of Figure 18K may be used to modify the embodiment of Figures 18G-18H. For example, core 1842 or core 1842' may be adapted to utilize a segmented shell 1804' with a space therebetween, or one or more strips of dielectric foam 1804". Similarly, core 1842 or core 1842' may be adapted into a non-circular core 1801' which may have a symmetrical or asymmetrical cross-sectional configuration. In addition, core 1842 or core 1842' may be adapted for use with multiple cores 1801" in a single inner waveguide, or when multiple inner waveguides Waveguides are used with different numbers of cores. Therefore, any of the embodiments shown in FIG. 18K can be applied to the embodiments 18G to 18H either singly or in combination.

Turning now to FIG. 18L , there is shown a block diagram illustrating an example non-limiting embodiment of bundled transmission media for crosstalk mitigation in accordance with various aspects described herein. In an embodiment, bundled transmission medium 1836 ′ may include variable core structure 1803 . By varying the core structure 1803, the fields of the guided electromagnetic waves induced in each of the cores of the transmission medium 1836' can be sufficiently different to reduce crosstalk between the cables 1838. In another embodiment, the bundled transmission medium 1836" may include a variable number of cores 1803' per cable 1838. By varying the number of cores 1803' per cable 1838, one or more of the transmission medium 1836" The fields of the guided electromagnetic waves induced in the cores may be sufficiently different to reduce crosstalk between the cables 1838 . In another embodiment, the core 1803 or 1803' can be made of different materials. For example, core 1803 or 1803' may be dielectric core 1802, insulated conductor core 1825, bare conductor core 1832, or any combination thereof.

It should be noted that the embodiments illustrated in FIGS. 18A-18D and 18F-18H may be modified from and/or combined with some of the embodiments of FIGS. 18K-18L . It should be further noted that one or more of the embodiments illustrated in Figures 18K-18L may be combined (eg, using segmented dielectric foam 1804' or having core 1801', 1801", 1803, or 1803' spiral dielectric foam strip 1804"). In some embodiments, guided electromagnetic waves propagating in transmission media 1800', 1800", 1800"' and/or 1800"" of FIG. Propagated guided electromagnetic waves suffer less propagation loss. Additionally, the embodiments illustrated in FIGS. 18K-18L can be adapted for use with the connection embodiments illustrated in FIGS. 18I-18J .

Turning now to FIG. 18M , a block diagram illustrating an example non-limiting embodiment of an exposed tapered stub from bundled transmission medium 1836 for use as antenna 1855 is shown. Each antenna 1855 may serve as a directional antenna for radiating wireless signals directed to a wireless communication device, or for inducing electromagnetic wave propagation at the surface of a transmission medium (eg, a power line). In an embodiment, the wireless signals radiated by the antennas 1855 may be beam-steered by adapting the phase and/or other characteristics of the wireless signals generated by each antenna 1855 . In an embodiment, the antenna 1855 may be placed separately in a pan-bottomed antenna assembly for directing wireless signals in all directions.

It should be further noted that the terms "core", "cladding", "shell" and "foam" as used in the subject disclosure may include Any type of material (or combination of materials) that propagates longitudinally along the core while remaining confined within the core. For example, the "dielectric foam 1804 tape" described earlier may be replaced with a tape of common dielectric material (e.g., polyethylene) for wrapping around the dielectric core 1802 (herein simply referred to as a "wrap" for purposes of illustration). ). In this configuration, the average density of the wrap may be less due to the air spaces between the sections of the wrap. Thus, the effective dielectric constant of the wrap may be less than the dielectric constant of the dielectric core 1802 so that the guided electromagnetic waves remain confined within the core. Accordingly, any embodiments of the subject disclosure directed to materials for the core(s) and wrappings surrounding the core(s) may be structurally adapted and/or utilized to achieve a limited to The electromagnetic wave of the core(s) propagates along the core(s) while maintaining the result of the electromagnetic wave being modified by other dielectric materials. Additionally, a core as described in any of the embodiments of the subject disclosure may comprise, in whole or in part, an opaque material (eg, polyethylene) that is resistant to propagation of electromagnetic waves having an optical operating frequency. Accordingly, the electromagnetic waves guided and confined to the core will have a non-optical frequency range (eg, less than the lowest frequency of visible light).

18N, 18O, 18P, 18Q, 18R, 18S and 18T are block diagrams illustrating example non-limiting embodiments of waveguide devices for transmitting and receiving electromagnetic waves according to various aspects described herein. In an embodiment, FIG. 18N illustrates a front view of a waveguide device 1865 having a plurality of slots 1863 (eg, openings or apertures) for emitting electromagnetic waves with a radiating electric field (e-field) 1861 . In an embodiment, the radiating e-fields 1861 of pairs of symmetrically positioned slots 1863 (eg, north and south slots of waveguide 1865 ) may be directed away from each other (ie, oppositely polarized radial orientations with respect to cable 1862 ). While slots 1863 are shown as having a rectangular shape, other shapes, such as other polygons, scallops and arcs, ovals, and others, are equally possible. For purposes of illustration only, the term north will refer to the relative direction as shown in the figures. All references to other directions (eg, south, east, west, northwest, etc.) in the subject disclosure will be drawn with respect to north. In an embodiment, in order to achieve e-fields having opposite orientations at the north and south slots 1863, for example, the north and south slots 1863 may be arranged to have a distance of about one wavelength of the electromagnetic wave signal provided to these slots relative to each other. Circumferential distance. The waveguide 1865 may have a cylindrical cavity at the center of the waveguide 1865 to enable the cable 1862 to be placed. In one embodiment, cable 1862 may include insulated conductors. In another embodiment, cable 1862 may include uninsulated conductors. In yet another embodiment, the cable 1862 may include any of the previously described embodiments of the transmission core 1852 of the cable 1850 .

In one embodiment, the cable 1862 can be slid into the cylindrical cavity of the waveguide 1865 . In another embodiment, the waveguide 1865 may utilize an assembly mechanism (not shown). An assembly mechanism (e.g., a hinge or other suitable mechanism that provides a means for opening waveguide 1865 at one or more locations) may be used to enable waveguide 1865 to be placed on the outer surface of cable 1862 or otherwise separate The parts are assembled together to form waveguide 1865, as shown. According to these and other suitable embodiments, waveguide 1865 may be configured to wrap around cable 1862 like a loop.

FIG. 18O illustrates a side view of an embodiment of a waveguide 1865 . Waveguide 1865 may be adapted to have a hollow rectangular waveguide portion 1867 that receives electromagnetic waves 1866 generated by transmitter circuitry as previously described in the subject disclosure (see, e.g., FIGS. 1 and 10A ). . Electromagnetic waves 1866 may be distributed through hollow rectangular waveguide portion 1867 into hollow collar 1869 of waveguide 1865 . Rectangular waveguide portion 1867 and hollow collar 1869 may be constructed of a material suitable for sustaining electromagnetic waves within the hollow cavity of these components (eg, carbon fiber material). It should be noted that while waveguide portion 1867 is shown and described as having a hollow rectangular configuration, other shapes and/or other non-hollow configurations may be used. Specifically, waveguide portion 1867 may have a square or other polygonal cross-section, an arcuate or fan-shaped cross-section truncated to conform to the outer surface of cable 1862 , a circular or elliptical cross-section or cross-sectional shape. Additionally, waveguide portion 1867 may be configured as or otherwise comprise a solid dielectric material.

As previously mentioned, the hollow collar 1869 may be configured to emit electromagnetic waves from each slot 1863 having opposite e-fields 1861 at the pair of symmetrically positioned slots 1863 and 1863'. In an embodiment, electromagnetic waves emitted by the combination of slots 1863 and 1863' may in turn induce electromagnetic waves 1868 that will be confined to cable 1862 so that in the absence of other wave modes, such as non-fundamental modes, Propagation is performed according to the fundamental mode. In this configuration, electromagnetic waves 1868 can propagate longitudinally along cable 1862 to other downstream waveguide systems coupled to cable 1862 .

It should be noted that since the hollow rectangular waveguide portion 1867 of FIG. 18O is closer to the slot 1863 (at the northern location of the waveguide 1865), the slot 1863 can emit electromagnetic waves with stronger electromagnetic waves than those emitted by the slot 1863' (at the southern location). amplitude of electromagnetic waves. To reduce the amplitude difference between these slots, slot 1863' can be made larger than slot 1863. The technique of using different slot sizes to balance signal amplitude between slots can be applied to any of the embodiments of the subject disclosure related to FIGS. 18N, 18O, 18Q, 18S, 18U, and 18V - some of which are described below .

In another embodiment, FIG. 18P depicts a waveguide 1865' that may be configured for use with circuitry, such as a monolithic microwave integrated circuit, each coupled to a signal input 1872 (eg, a coaxial cable providing a communication signal). Circuit (MMIC) 1870. Signal input 1872 may be generated by a transmitter circuit adapted to provide electrical signals to MMIC 1870 as previously described in the subject disclosure (eg, see reference numerals 101 , 1000 of FIGS. 1 and 10A ). Each MMIC 1870 may be configured to receive a signal 1872 which may be modulated and transmitted using a radiating element (eg, an antenna) to transmit electromagnetic waves having a radiating e-field 1861 . In one embodiment, the MMIC 1870 may be configured to receive the same signal 1872, but emit electromagnetic waves with an e-field 1861 of opposite orientation. This may be accomplished by configuring one of the MMICs 1870 to emit electromagnetic waves 180 degrees out of phase with those emitted by the other MMIC 1870 . In an embodiment, the combination of electromagnetic waves emitted by the MMIC 1870 may together induce electromagnetic waves 1868 that are confined to the cable 1862 so that in the absence of other wave modes, such as non-fundamental modes, to propagate. In this configuration, electromagnetic waves 1868 can propagate longitudinally along cable 1862 to other downstream waveguide systems coupled to cable 1862 .

As depicted in FIGS. 18Q and 18R , a tapered horn 1880 may be added to the embodiment of FIGS. 18O and 18P to assist in inducing electromagnetic waves 1868 on cable 1862 . In embodiments where cable 1862 is an uninsulated conductor, electromagnetic waves induced on cable 1862 may have a larger radial dimension (eg, 1 meter). To enable the use of a smaller tapered horn 1880, an insulating layer 1879 may be applied over a portion of the cable 1862 located at or near the cavity as depicted with dashed lines in Figures 18Q and 18R. The insulating layer 1879 may have a tapered end facing away from the waveguide 1865 . The added insulator enables tight confinement of the electromagnetic wave 1868 originally emitted by the waveguide 1865 (or 1865') to the insulator, which in turn reduces the radial dimension (eg, centimeters) of the electromagnetic field 1868. As the electromagnetic wave 1868 propagates away from the waveguide 1865 (1865') and reaches the tapering end of the insulation 1879, the radial dimension of the electromagnetic wave 1868 begins to increase, eventually achieving Electromagnetic waves 1868 are generated and these electromagnetic waves will have a radial dimension of . In the illustrations of FIGS. 18Q and 18R , the tapered end begins at one end of the tapered horn 1880 . In other embodiments, the tapered end of the insulating layer 1879 may start before or after the end of the tapered horn 1880 . The tapered horn may be metallic, or constructed of other conductive material, or constructed of plastic or other non-conductive material coated or clad with a dielectric layer or doped with a conductive material to provide reflective properties similar to a metal horn .

In an embodiment, the cable 1862 may comprise any of the earlier described embodiments of the cable 1850 . In this embodiment, waveguides 1865 and 1865' may be coupled to transmission core 1852 of cable 1850 as depicted in FIGS. 18S and 18T. As previously described, waveguides 1865 and 1865' may induce electromagnetic waves 1868 on transmission core 1852 to propagate fully or partially within the inner layer of cable 1850.

It should be noted that for the previous embodiments of Figures 18Q, 18R, 18S, and 18T, the electromagnetic wave 1868 may be bi-directional. For example, electromagnetic waves 1868 of different operating frequencies may be received by slots 1863 or MMIC 1870 of waveguides 1865 and 1865', respectively. Once received, the electromagnetic waves may be converted by receiver circuitry (eg, see reference numerals 101, 1000 of FIGS. 1 and 1OA) to generate communication signals for processing.

Although not shown, it should be further noted that waveguides 1865 and 1865' may be adapted such that waveguides 1865 and 1865' may direct electromagnetic wave 1868 longitudinally up or down. For example, a first tapered horn 1880 coupled to a first instance of the waveguide 1865 or 1865' may be directed westward on the cable 1862, while a second tapered horn coupled to a second instance of the waveguide 1865 or 1865' may be directed westward on the cable 1862. Horn 1880 may be directed eastward on cable 1862. The first and second instances 1865 or 1865' of waveguides may be coupled such that in a repeater configuration, signals received by the first waveguide 1865 or 1865' may be provided to the second waveguide 1865 or 1865' for Retransmissions are made on cable 1862 in the east direction. The repeater configuration just described can also be applied on cable 1862 from east to west direction.

The waveguides 1865 of Figures 18N, 18O, 18Q, and 18S may also be configured to generate electromagnetic fields with only non-fundamental or asymmetric wave modes. Figure 18U depicts an embodiment of a waveguide 1865 that may be adapted to generate an electromagnetic field with only non-fundamental modes. The center line 1890 represents the space between the slots where the current on the backside (not shown) of the front plate of the waveguide 1865 changes polarity. For example, in some embodiments, currents corresponding to e-fields on the backside of the front plate corresponding to radially outward (i.e., pointing away from the center point of cable 1862) may be associated with slots located outside centerline 1890 (e.g., slots 1863A and 1863B). In some embodiments, a current on the backside of the front plate corresponding to an e-field radially inward (ie, pointing toward the center point of cable 1862 ) may be associated with a slot located within centerline 1890 . The direction of the current flow may depend on the operating frequency of the electromagnetic wave 1866 provided to the hollow rectangular waveguide portion 1867 (see FIG. 180 ), among other parameters.

For purposes of illustration, it is assumed that the electromagnetic wave 1866 supplied to the hollow rectangular waveguide portion 1867 has an operating frequency by which the circumferential distance between the slots 1863A and 1863B is one full wavelength of the electromagnetic wave 1866 . In this example, the e-fields of electromagnetic waves emitted by slots 1863A and 1863B are directed radially outward (ie, have opposite orientations). When the electromagnetic waves emitted by slots 1863A and 1863B are combined, the resulting electromagnetic waves on cable 1862 will propagate according to the fundamental wave mode. In contrast, by repositioning (e.g., slot 1863C) one of the slots (i.e., slot 1863B) within dielectric wire 1890, slot 1863C will generate an e-field having an e-field approximately 180 degrees from the electromagnetic wave generated by slot 1863A. Electromagnetic waves of phase e field. Thus, the e-field orientations of the electromagnetic waves generated by slot pair 1863A and 1863C will be substantially aligned. The combination of electromagnetic waves emitted by slot pair 1863A and 1863C will thus generate electromagnetic waves that are confined to cable 1862 so as to propagate according to non-fundamental modes.

To achieve a reconfigurable slot arrangement, the waveguide 1865 can be adapted according to the embodiment depicted in Figure 18V. Configuration (A) depicts a waveguide 1865 with multiple symmetrically positioned slots. Each slot 1863 of configuration (A) can be selectively disabled by blocking the slots 1863 with some material (eg, carbon fiber or metal) to prevent emission of electromagnetic waves. Blocked (or disabled) slots 1863 are shown in black, while enabled (or unblocked) slots 1863 are shown in white. Although not shown, blocking material may be placed behind (or in front of) the front plate of waveguide 1865 . A mechanism (not shown) can be coupled to the barrier material so that the barrier material can slide in and out of specific slots 1863, like a cover to close or open a window. The mechanism may be coupled to a linear motor controllable by the circuitry of the waveguide 1865 to selectively enable or disable individual slots 1863 . With this mechanism at each slot 1863, the waveguide 1865 can be configured to select different configurations of enabled and disabled slots 1863, as depicted in the embodiment of Figure 18V. Other methods or techniques for capping or uncapping slots (eg, utilizing a rotatable disk behind or in front of waveguide 1865) may be applied to embodiments of the subject disclosure.

In one embodiment, as shown in configuration (B), the waveguide system 1865 may be configured to enable certain slots 1863 outside the centerline 1890 and disable certain slots 1863 inside the centerline 1890 in order to generate the fundamental . For example, assume that the circumferential distance between slots 1863 outside centerline 1890 (ie, in the northern and southern locations of waveguide system 1865) is one full wavelength. Consequently, the slots will have an electric field (e-field) directed radially outward at some point as previously described. In contrast, the slots within the centerline 1890 (ie, in the west and east locations of the waveguide system 1865) will have a circumferential distance of half a wavelength relative to any of the slots 1863 outside the centerline. Since the slots within the centerline 1890 are separated by half a wavelength, these slots will generate electromagnetic waves with e-fields directed radially outward. If the west and east slots 1863 outside the centerline 1890 had been activated, rather than the west and east slots inside the centerline 1890, the e-fields emitted by those slots would have been directed radially inward, the e-fields being When combined with the north and south electric fields will result in non-fundamental mode propagation. Thus, a configuration (B) as depicted in FIG. 18V can be used to generate electromagnetic waves with radially outwardly directed e-fields at the north and south slots 1863 and equally radially directed e-fields at the west and east slots 1863. An electromagnetic wave of an outwardly directed e-field, which when combined induces an electromagnetic wave having a fundamental mode on the cable 1862 .

In another embodiment, as shown in Configuration (C), waveguide system 1865 may be configured to enable North, South, West, and East slots 1863, all of which are outside centerline 1890, and to disable all Other slots 1863. Assuming the circumferential distance between a pair of opposing slots (e.g., north and south, or west and east) is a full wavelength apart, configuration (C) can be used to generate Electromagnetic waves in a non-fundamental mode radially inward. In yet another embodiment, as shown in configuration (D), the waveguide system 1865 can be configured to enable the NW slot 1863 outside the centerline 1890, enable the SE slot 1863 inside the centerline 1890, and disable all The other slots of 1863. Assuming the circumferential distance between such a pair of slots is a full wavelength apart, this configuration can be used to generate electromagnetic waves in non-fundamental modes with e-fields aligned in the northwest direction.

In another embodiment, the waveguide system 1865 may be configured to generate electromagnetic waves having a non-fundamental mode with the e-field aligned in a southwest direction. This can be achieved by utilizing a different arrangement than that used in configuration (D). As shown in configuration (E), configuration (E) can be achieved by enabling the southwest slot 1863 outside the centerline 1890 , enabling the northeast slot 1863 inside the centerline 1890 , and disabling all other slots 1863 . Assuming the circumferential distance between such a pair of slots is a full wavelength apart, this configuration can be used to generate electromagnetic waves in non-fundamental modes with e-fields aligned in the southwest direction. Configuration (E) thus generates non-fundamental modes that are orthogonal to those of configuration (D).

In yet another embodiment, the waveguide system 1865 may be configured to generate electromagnetic waves having a fundamental mode whose e-field is directed radially inward. As shown in configuration (F), this can be achieved by activating the north channel 1863 within the centerline 1890, activating the south channel 1863 within the centerline 1890, activating the east channel 1890 outside the centerline 1890, activating the west channel 1890 outside the centerline 1890 slot 1863, and disable all other slots 1863. Assuming the circumferential distance between the north and south slots is a full wavelength apart, this configuration can be used to generate electromagnetic waves with a fundamental mode with a radially inward e-field. Although the slots selected in configurations (B) and (F) are different, the fundamental modes generated by configurations (B) and (F) are the same.

In yet another embodiment, the e-field can be manipulated between the slots to generate fundamental or non-fundamental modes by varying the operating frequency of the electromagnetic wave 1866 provided to the hollow rectangular waveguide portion 1867 . For example, assume that for a particular operating frequency of electromagnetic wave 1866 in the illustration of FIG. 18U , the circumferential distance between slots 1863A and 1863B is one full wavelength of electromagnetic wave 1866 . In this example, the e-fields of the electromagnetic waves emitted by the slots 1863A and 1863B would point radially outward as shown, and may be used in combination to induce electromagnetic waves in the fundamental mode on the cable 1862 . In contrast, the e-fields of the electromagnetic waves emitted by the slots 1863A and 1863C will be radially aligned (i.e., pointing north) as shown, and can be used in combination to induce radiation with non-fundamental modes on the cable 1862. electromagnetic waves.

Suppose now that the operating frequency of electromagnetic wave 1866 supplied to hollow rectangular waveguide portion 1867 is changed such that the circumferential distance between grooves 1863A and 1863B is half the wavelength of electromagnetic wave 1866 . In this example, the e-fields of electromagnetic waves emitted by slots 1863A and 1863B will be radially aligned (ie, point in the same direction). That is, the e-field of the electromagnetic wave emitted by the slot 1863B will point in the same direction as the e-field of the electromagnetic wave emitted by the slot 1863A. Such electromagnetic waves may be used in combination to induce electromagnetic waves on cable 1862 having non-fundamental modes. In contrast, the e-fields of electromagnetic waves emitted by slots 1863A and 1863C will be radially outward (ie, away from cable 1862 ) and can be used in combination to induce electromagnetic waves in the fundamental mode on cable 1862 .

In another embodiment, the waveguide 1865' of Figures 18P, 18R and 18T may also be configured to generate electromagnetic waves having only non-fundamental modes. This can be achieved by adding more MMICs 1870, as depicted in Figure 18W. Each MMIC 1870 may be configured to receive the same signal input 1872 . However, the MMICs 1870 may be selectively configured to transmit electromagnetic waves with different phases using controllable phase shift circuitry in each MMIC 1870 . For example, the north and south MMICs 1870 may be configured to emit electromagnetic waves with a 180 degree phase difference, so that the e-fields are aligned in a north or south direction. Any combination of pairs of MMICs 1870 (eg, West and East MMICs 1870, Northwest and Southeast MMICs 1870, Northeast and Southeast MMICs 1870) may be configured with opposite or aligned e-fields. Accordingly, waveguide 1865' may be configured to generate electromagnetic waves having one or more non-fundamental modes, electromagnetic waves having one or more fundamental modes, or any combination thereof.

Applicants believe that it is not necessary to select the slots 1863 in pairs to generate electromagnetic waves with non-fundamental modes. For example, electromagnetic waves with non-fundamental modes can be generated by enabling a single slot from the plurality of slots shown in configuration (A) of FIG. 18V and disabling all other slots. Similarly, a single MMIC 1870 of the MMICs 1870 shown in FIG. 18W may be configured to generate electromagnetic waves with non-fundamental modes when all other MMICs 1870 are unused or disabled. Likewise, other wave modes and combinations of wave modes can be induced by enabling waveguide slots 1863 or other non-empty appropriate subsets of MMICs 1870 .

Applicants further believe that the e-field arrows shown in Figures 18U-18V are illustrative only and represent a static depiction of the e-field. In fact, an electromagnetic wave can have an oscillating e-field that points outward at one moment and inward at another. For example, in the case of a non-fundamental mode with an e-field aligned in one direction (eg, north), such a wave may at another moment have an e-field pointing in the opposite direction (eg, south). Similarly, a fundamental mode with a radial e-field may have an e-field pointing radially away from the cable 1862 at one moment and pointing radially toward the cable 1862 at another moment. It should be further noted that the embodiments of FIGS. 18U-18W can be adapted to generate electromagnetic waves with one or more non-fundamental modes, electromagnetic waves with one or more fundamental modes (e.g., TM00 mode and HE11 mode), or any combination thereof. It should be further noted that this adaptation may be used in combination with any of the embodiments described in the subject disclosure. It should also be noted that the embodiments of Figures 18U-18W can be combined (eg, slots used in combination with MMICs).

It should be further noted that, in some embodiments, the waveguide systems 1865 and 1865' of FIGS. 18N-18W may generate combinations of fundamental and non-fundamental modes in which one wave mode dominates the other. kind of wave pattern. For example, in one embodiment, electromagnetic waves generated by waveguide systems 1865 and 1865' of FIGS. 18N-18W may have weak signal components with non-fundamental modes and relatively strong signal components with fundamental modes. Therefore, in this embodiment, the electromagnetic wave has a substantially fundamental wave mode. In another embodiment, the electromagnetic waves generated by the waveguide systems 1865 and 1865' of FIGS. 18N-18W may have weak signal components with fundamental modes and relatively strong signal components with non-fundamental modes. Thus, in this embodiment, the electromagnetic waves have substantially non-fundamental modes. Further, non-dominant wave modes can be generated that propagate only insignificant distances along the length of the transmission medium.

It should also be noted that waveguide systems 1865 and 1865' of FIGS. 18N-18W may be configured to generate an instance of electromagnetic waves having wave modes that may differ from the resulting wave mode or modes of the combined electromagnetic waves. It should be further noted that each MMIC 1870 of the waveguide system 1865' of FIG. instance. For example, one MMIC 1870 may generate an electromagnetic wave having a different spatial orientation and phase, frequency, amplitude, electric field orientation, and/or magnetic field orientation than another instance of an electromagnetic wave generated by another MMIC 1870. Examples of electromagnetic waves of amplitude, electric field orientation, and/or magnetic field orientation. The waveguide system 1865' may thus be configured to generate instances of electromagnetic waves having different wave and spatial characteristics that, when combined, result in a generated electromagnetic wave having one or more desired wave modes.

From these illustrations, Applicants believe that the waveguide systems 1865 and 1865' of FIGS. 18N-18W may be adapted to generate electromagnetic waves having one or more selectable wave modes. In one embodiment, for example, waveguide systems 1865 and 1865' may be adapted to select one or more wave modes and generate electromagnetic waves having a combination of one or more configurable wave and spatial characteristics. Electromagnetic waves of a single wave mode or multiple wave modes selected and generated during the process. In an embodiment, for example, parameter information may be stored in a lookup table. Each entry in the lookup table can represent a selectable wave mode. The selectable wave modes may represent a single wave mode, or a combination of wave modes. A combination of wave modes can have one or the dominant wave mode. The parameter information may provide configuration information for an instance of generating an electromagnetic wave in order to produce a resulting electromagnetic wave having a desired wave pattern.

For example, once one or more wave modes are selected, parameter information obtained from a lookup table from entries associated with the selected wave mode(s) can be used to identify Which of the one or more MMICs 1870, and/or their corresponding configurations, is to be utilized for the electromagnetic wave of the selected mode. The parametric information may identify a selection of one or more MMICs 1870 based on the spatial orientation of the MMICs 1870, which may be required to generate electromagnetic waves having a desired wave pattern. The parameter information may also provide information to configure each of the one or more MMICs 1870 with a particular phase, frequency, amplitude, electric field orientation, and/or or magnetic field orientation. A look-up table with selectable wave modes and corresponding parameter information can be adapted to configure the slotted waveguide system 1865 .

In some embodiments, if a wave mode travels a non-insignificant distance on the transmission medium and has a field strength that is significantly greater in magnitude than other wave modes that may or may not be desirable (e.g., 20 dB higher in magnitude), then the corresponding A guided electromagnetic wave can be thought of as having a desired wave pattern. Such one or more desired wave modes may be referred to as dominant wave modes(s), while other wave modes are referred to as non-dominant wave modes. In a similar manner, guided electromagnetic waves that are considered to have substantially no fundamental modes have either no fundamental modes or non-dominant fundamental modes. A guided electromagnetic wave that is considered to have substantially no non-fundamental modes has either no non-fundamental mode(s) or only non-dominant non-fundamental modes. In some embodiments, a guided electromagnetic wave that is considered to have only a single or selected wave mode may have only one corresponding dominant wave mode.

It should be further noted that the embodiments of Figures 18U-18W can be applied to other embodiments of the subject disclosure. For example, the embodiment of Figures 18U-18W may be used as an alternative to, or may be combined with, the embodiment depicted in Figures 18N-18T.

Turning now to FIGS. 19A and 19B , block diagrams illustrating example non-limiting embodiments of dielectric antennas and corresponding gain and field strength graphs in accordance with various aspects described herein are shown. Figure 19A depicts a dielectric horn antenna 1901 having a conical structure. Dielectric horn antenna 1901 is coupled to one end 1902' of feed line 1902 having a feed point 1902" at the opposite end of feed line 1902. Dielectric horn antenna 1901 and feed line 1902 (and described below in the subject disclosure Other embodiments of a dielectric antenna) may be constructed of a dielectric material, such as polyethylene material, polyurethane material, or other suitable dielectric material (e.g., synthetic resin, other plastic, etc.). Dielectric horn antenna 1901 and feeder 1902 (and hereinafter in this Other embodiments of the dielectric antenna described in the subject disclosure) can be adapted to be substantially free or completely free of any conductive material.

For example, the outer surface 1907 of the dielectric horn antenna 1901 and the feedline 1902 can be non-conductive or substantially non-conductive, wherein at least 95% of the outer surface area is non-conductive and used to construct the dielectric horn antenna 1901 and the feedline 1902 The dielectric materials may be such that they are substantially free (eg, such as less than one part in a thousand) of impurities that could be conductive or would cause to impart conductive properties. However, in other embodiments, a limited number of conductive components may be used, such as feed points for coupling to feed line 1902 using one or more screws, rivets, or other coupling elements for bonding components to each other. 1902"; and/or one or more structural elements that do not significantly alter the radiation pattern of the dielectric antenna.

The feed point 1902" can be adapted to couple to the core 1852, such as previously described by the illustrations in Figures 18I and 18J. In one embodiment, the feed point 1902" can utilize a splicing device such as that of Figure 18J A connector (not shown in FIG. 19A ) of 1860 is coupled to core 1852 . Other embodiments for coupling feed point 1902 ″ to core 1852 may be used. In an embodiment, a joint may be configured for feed point 1902 ″ to contact an end of core 1852 . In another embodiment, the joint can create a gap between the feed point 1902" and the end of the core 1852. In yet another embodiment, the joint can have the feed point 1902" and the core 1852 coaxially aligned or partially Misaligned. Notwithstanding any combination of the preceding embodiments, the electromagnetic wave may propagate entirely or at least partially between the feed point 1902 ″ and the junction of the core 1852 .

Cable 1850 may be coupled to waveguide system 1865 depicted in Figure 18S or waveguide system 1865' depicted in Figure 18T. For purposes of illustration only, reference will be made to the waveguide system 1865' of Figure 18T. However, it should be understood that the waveguide system 1865 of FIG. 18S or other waveguide systems may also be utilized in accordance with the discussion below. The waveguide system 1865' can be configured to select wave modes (e.g., non-fundamental modes, fundamental modes, hybrid wave modes, or combinations thereof as described earlier) and to transmit waves having a non-optical frequency of operation (e.g., 60 GHz) An example of electromagnetic waves. Electromagnetic waves may be directed to the interface of cable 1850 as shown in FIG. 18T .

An example of electromagnetic waves generated by waveguide system 1865' may induce a combined electromagnetic wave having a selected wave mode that propagates from core 1852 to feed point 1902". The combined electromagnetic wave may propagate partially inside core 1852 and partially within core 1852. Once the combined electromagnetic wave has propagated through the junction between the core 1852 and the feed point 1902″, the combined electromagnetic wave may continue to propagate partly inside the feeder 1902 and partly on the outer surface of the feeder 1902. In some embodiments, less of the combined electromagnetic wave propagates on the outer surfaces of core 1852 and feeder 1902 . In these embodiments, the combined electromagnetic wave can be considered to be guided by and tightly coupled to the core 1852 and the feeder 1902 while propagating longitudinally towards the dielectric antenna 1901 .

When the combined electromagnetic wave reaches the proximal portion of the dielectric antenna 1901 (at the junction 1902′ between the feeder 1902 and the dielectric antenna 1901), the combined electromagnetic wave enters the proximal portion of the dielectric antenna 1901 and propagates longitudinally along the axis of the dielectric antenna 1901 ( shown as dashed lines). By the time the combined electromagnetic wave reaches the aperture 1903, the combined electromagnetic wave has an intensity diagram similar to that shown by the side and front views depicted in Figure 19B. The electric field strength graph of FIG. 19B shows that the electric field of the combined electromagnetic wave is strongest in the central region of the aperture 1903 and weaker in the outer region. In an embodiment, where the wave mode of the electromagnetic waves propagating in the dielectric antenna 1901 is a hybrid wave mode (eg, HE11), leakage of electromagnetic waves at the outer surface 1907 is reduced or in some cases eliminated. It should be further noted that although the dielectric antenna 1901 is constructed of a solid dielectric material with no physical openings, the front or operating face of the dielectric antenna 1901 from which free space wireless signals are radiated or received will be referred to as the aperture 1903 of the dielectric antenna 1901 , even in some prior art systems, the term aperture may be used to describe the opening of an antenna that radiates or receives free-space wireless signals. Methods for transmitting the mixed wave mode on cable 1850 are discussed below.

In an embodiment, the far-field antenna gain plot depicted in FIG. 19B can be widened by reducing the operating frequency of the combined electromagnetic wave from the nominal frequency. Similarly, the gain map can be narrowed by increasing the operating frequency of the combined electromagnetic wave relative to the nominal frequency. Thus, the width of the wireless signal beam emitted by aperture 1903 can be controlled by configuring waveguide system 1865' to increase or decrease the operating frequency of the combined electromagnetic wave.

The dielectric antenna 1901 of FIG. 19A can also be used to receive wireless signals, such as free space wireless signals transmitted by similar or conventional antenna designs. The wireless signal received by the dielectric antenna 1901 at the aperture 1903 induces in the dielectric antenna 1901 electromagnetic waves propagating toward the feeder line 1902 . Electromagnetic waves continue to propagate from the feed line 1902 to the junction between the feed point 1902" and the end of the core 1852, and from there are delivered to the waveguide system 1865' coupled to the cable 1850 as shown in Figure 18T. In this configuration, the waveguide System 1865' may utilize dielectric antenna 1901 to perform two-way communication. It should be further noted that in some embodiments, core 1852 (shown in dashed lines) of cable 1850 may be configured to be in-line with feed point 1902" to avoid The bend shown in Figure 19A. In some embodiments, the collinear configuration can reduce variations in electromagnetic propagation due to bends in the cable 1850 .

Turning now to FIGS. 19C and 19D , there are shown example diagrams illustrating a dielectric antenna 1901 coupled to or integrally constructed with a lens 1912 and corresponding gain and field strength graphs in accordance with various aspects described herein. Block diagram of a limiting embodiment. In one embodiment, lens 1912 may include a dielectric material having a first dielectric constant that is substantially similar or equal to a second dielectric constant of dielectric antenna 1901 . In other embodiments, lens 1912 may include a dielectric material having a first dielectric constant that is different from a second dielectric constant of dielectric antenna 1901 . In any of these embodiments, the shape of the lens 1912 may be selected or formed to equalize the delay of these various electromagnetic waves propagating at different points in the dielectric antenna 1901 . In one embodiment, the lens 1912 may be an integral part of the dielectric antenna 1901 as depicted in the top view of FIG. formed in other ways. Alternatively, as depicted in the bottom view of FIG. 19C , lens 1912 may be an assembled component of dielectric antenna 1901 that may be attached by adhesive material, brackets on the outer edges, or other suitable attachment techniques. The lens 1912 may have a convex structure as shown in FIG. 19C adapted to adjust the propagation of electromagnetic waves in the dielectric antenna 1901 . While a circular lens and conical dielectric antenna configuration are shown, other shapes including pyramidal shapes, elliptical shapes, and other geometric shapes can be implemented as well.

In particular, the curvature of lens 1912 may be selected in a manner that reduces the phase difference between near-field wireless signals generated by aperture 1903 of dielectric antenna 1901 . The lens 1912 accomplishes this by applying a position-dependent delay to the propagating electromagnetic wave. Due to the curvature of the lens 1912, the delay differs depending on where the electromagnetic wave originates at the aperture 1903. For example, electromagnetic waves propagating through central axis 1905 of dielectric antenna 1901 will experience more delay through lens 1912 than electromagnetic waves propagating radially away from central axis 1905 . For example, electromagnetic waves propagating towards the outer edge of aperture 1903 will experience minimal or no delay through the lens. The propagation delay increases as the electromagnetic wave approaches the central axis 1905 . Accordingly, the curvature of lens 1912 may be configured such that near-field wireless signals have substantially similar phases. By reducing the difference between the phases of the near-field wireless signals, the width of the far-field signal generated by the dielectric antenna 1901 is reduced, which in turn increases the The strength of the far-field wireless signal within the width of the main lobe, resulting in a relatively narrow beam pattern with high gain.

Turning now to FIGS. 19E and 19F , diagrams illustrating a dielectric antenna 1901 coupled to a lens 1912 having a ridge (or step) 1914 and corresponding gain and field strength graphs in accordance with various aspects described herein are shown. Block diagram of an exemplary non-limiting embodiment. In these illustrations, lens 1912 may include concentric ridges 1914 shown in the side and perspective views of Figure 19E. Each ridge 1914 may include a riser 1916 and a tread 1918 . The size of the tread 1918 varies according to the curvature of the aperture 1903 . For example, the treads 1918 at the center of the aperture 1903 may be larger than the treads at the outer edges of the aperture 1903 . To reduce reflection of electromagnetic waves reaching aperture 1903, each raised portion 1916 may be configured to have a depth representing a selected wavelength factor. For example, raised portion 1916 may be configured to have a depth of a quarter wavelength of electromagnetic waves propagating in dielectric antenna 1901 . This configuration causes electromagnetic waves reflected from one raised portion 1916 to have a phase difference of 180 degrees with respect to electromagnetic waves reflected from an adjacent raised portion 1916 . Accordingly, out-of-phase electromagnetic waves reflected from adjacent raised portions 1916 substantially cancel, thereby reducing reflections and distortions resulting therefrom. While a particular rise/tread configuration is shown, other configurations with different numbers of rises, different rise shapes, etc. may likewise be implemented. In some embodiments, the lens 1912 with concentric ridges depicted in Figure 19E may experience less reflection of electromagnetic waves than the lens 1912 with the smooth convex surface depicted in Figure 19C. Figure 19F depicts a graph of the resulting far-field gain of the dielectric antenna 1901 of Figure 19E.

Turning now to FIG. 19G , there is shown a block diagram illustrating an example non-limiting embodiment of a dielectric antenna 1901 having an elliptical configuration in accordance with various aspects described herein. FIG. 19G depicts side, top and front views of dielectric antenna 1901 . The elliptical shape is achieved by reducing the height of the dielectric antenna 1901 as shown by reference number 1922 and by lengthening the dielectric antenna 1901 as shown by reference number 1924 . The resulting oval shape 1926 is shown in the front view depicted by Figure 19G. The elliptical shape may be formed via machining using dies or other suitable construction techniques.

Turning now to FIG. 19H , there is shown a block diagram illustrating an example non-limiting embodiment of near-field signal 1928 and far-field signal 1930 transmitted by dielectric antenna 1901 of FIG. 19G in accordance with various aspects described herein. The cross-section of the near-field beam pattern 1928 mimics the elliptical shape of the aperture 1903 of the dielectric antenna 1901 . The cross-section of the far-field beam pattern 1930 has a rotational offset (approximately 90 degrees) caused by the elliptical shape of the near-field signal 1928 . The offset may be determined by applying a Fourier transform to the near-field signal 1928 . Although the cross-section of the near-field beam pattern 1928 and the far-field beam pattern 1930 are shown to be nearly the same size in order to demonstrate the effect of rotation, the actual size of the far-field beam pattern 1930 may increase with distance from the dielectric antenna 1901 big.

The elongated shape of the far field signal 1930 and its orientation may prove useful when aligning the dielectric antenna 1901 with respect to a remotely located receiver configured to receive the far field signal 1930 . The receiver may include one or more dielectric antennas coupled to a waveguide system as described by the subject disclosure. The extended far field signal 1930 may increase the likelihood that a remotely located receiver will detect the far field signal 1930 . Additionally, the extended far-field signal 1930 may be useful in situations where the dielectric antenna 1901 is coupled to a gimbal assembly as shown in FIG. 19M or to other actuated antenna mounts including, but not limited to Attorney Docket No. 2015-0603_7785-1210, entitled COMMUNICATION DEVICE AND ANTENNA ASSEMBLY WITH ACTUATED GIMBAL MOUNT, filed October 2, 2015, and U.S. Patent An actuated gimbal mount as described in co-pending application Ser. No. 14/873,241, the contents of which are hereby incorporated by reference for any and all purposes. Specifically, the extended far-field signal 1930 may be in a mount such as a gimbal with only two degrees of freedom for aligning the dielectric antenna 1901 in the direction of the receiver (e.g., yaw and pitch are adjustable, but roll Useful in cases where the rotation is fixed).

Although not shown, it should be appreciated that the dielectric antenna 1901 of FIGS. 19G and 19H may have an integrated or attachable lens 1912 as shown in FIGS. to increase the strength of the far-field signal 1930.

Turning now to FIG. 191 , shown is a block diagram of an example, non-limiting embodiment of a dielectric antenna 1901 for conditioning far-field wireless signals in accordance with various aspects described herein. In some embodiments, the width of the far-field wireless signal generated by the dielectric antenna 1901 can be considered to be related to the number of wavelengths of electromagnetic waves propagating in the dielectric antenna 1901 that can fit in the surface area of the aperture 1903 of the dielectric antenna 1901 Inversely proportional. Thus, as the wavelength of the electromagnetic wave increases, the width of the far-field wireless signal increases proportionally (and its strength decreases). In other words, as the frequency of electromagnetic waves decreases, the width of the far-field wireless signal increases proportionally. Therefore, to enhance the process of aligning the dielectric antenna 1901 in the direction of the receiver using, for example, a gimbal assembly as shown in FIG. is reduced so that the far-field wireless signal is wide enough to increase the likelihood that a receiver will detect a portion of the far-field wireless signal.

In some embodiments, the receiver may be configured to perform measurements on far-field wireless signals. From these measurements, the receiver can direct the waveguide system coupled to the dielectric antenna 1901 that generates the far-field wireless signal. The receiver can provide commands to the waveguide system through an omnidirectional wireless signal or a tethered interface between them. Instructions provided by the receiver may cause the waveguide system to control actuators in the gimbal assembly coupled to the dielectric antenna 1901 to adjust the direction of the dielectric antenna 1901 to improve alignment of the dielectric antenna with the receiver. As the quality of the far-field wireless signal improves, the receiver can also direct the waveguide system to increase the frequency of the electromagnetic waves, which in turn reduces the width and correspondingly increases the strength of the far-field wireless signal.

In an alternative embodiment, an absorbing sheet 1932 composed of carbon or conductive material and/or other absorbers may be embedded in the dielectric antenna 1901, as depicted by the perspective and front views shown in Figure 19I. When the electric field of the electromagnetic wave is parallel to the absorbing sheet 1932, the electromagnetic wave is absorbed. However, the gap region 1934 in which the absorbing sheet 1932 is absent will allow electromagnetic waves to propagate to the aperture 1903 and thereby emit near-field wireless signals approximately having the width of the gap region 1934 . By reducing the number of wavelengths to the surface area of the gap region 1932, the width of near-field wireless signals decreases, while the width of far-field wireless signals increases. This property can be useful during the alignment process described previously.

For example, the polarity of the electric field emitted by the electromagnetic wave may be configured to be parallel to the absorbing sheet 1932 at the beginning of the alignment process. When a remotely located receiver directs the waveguide system coupled to the dielectric antenna 1901 to direct the dielectric antenna 1901 using an actuator of the gimbal assembly or other actuated mount, the receiver may also direct the waveguide system to follow the Signal measurements performed by the receiver improve and incrementally adjust the alignment of the electromagnetic wave relative to the electric field of the absorbing sheet 1932 . As the alignment improves, eventually the waveguide system adjusts the electric fields so that they are normal to the absorbing sheet 1932 . At this point, the electromagnetic waves near the absorbing sheet 1932 will no longer be absorbed, and all or substantially all of the electromagnetic waves will propagate to the aperture 1903 . Since the near field wireless signal now covers all or substantially all of the aperture 1903, the far field signal will have a narrower width and higher intensity when directed to the receiver.

It should be appreciated that a receiver configured to receive far-field wireless signals (as described above) may also be configured to utilize a transmitter that transmits the signal directed to the dielectric antenna 1901, detected by the waveguide system. The wireless signal used. For purposes of illustration, such a receiver will be referred to as a remote system that can receive far-field wireless signals and transmit wireless signals directed to a waveguide system. In this embodiment, the waveguide system may be configured to analyze the wireless signal it receives through the dielectric antenna 1901 and determine whether the quality of the wireless signal generated by the remote system justifies further adjustments to the far-field signal pattern to improve the remote system's response to Whether reception of far-field wireless signals is reasonable and/or further orientation of the dielectric antenna via a gimbal (see FIG. 19M ) or other actuated mount is required. As the quality of reception of wireless signals by the waveguide system improves, the waveguide system can increase the operating frequency of electromagnetic waves, which in turn reduces the width and correspondingly increases the strength of the far-field wireless signal. In other modes of operation, the gimbal or other actuated mount may be periodically adjusted to maintain optimal alignment.

Combinations of the preceding embodiments of FIG. 19I are also possible. For example, the waveguide system may perform adjustments to the far-field signal pattern based on analysis of wireless signals generated by the remote system in combination with messages or instructions provided by the remote system indicating the quality of the far-field signal received by the remote system and/or Or antenna orientation adjustment.

Turning now to FIG. 19J , shown is a block diagram of an example non-limiting embodiment of a collar (eg, flange) 1942 that can be coupled to a dielectric antenna 1901 in accordance with various aspects described herein. The flange may be constructed of metal (eg aluminum) dielectric material (eg polyethylene and/or foam) or other suitable material. As shown in Figure 19K, a flange 1942 can be used to align the feed point 1902" (and, in some embodiments, the feed line 1902) with a waveguide system 1948 (e.g., a circular waveguide). To achieve this, the method The flange 1942 may include a central hole 1946 for engaging the feed point 1902". In one embodiment, bore 1946 may be threaded and feeder wire 1902 may have a smooth surface. In this embodiment, the flange 1942 may engage the feed point 1902" by inserting a portion of the feed point 1902" (composed of a dielectric material such as polyethylene) into the hole 1946 and rotating the flange 1942 to serve as a A complementary thread die is formed on the soft outer surface of the feeder wire 1902 .

Once the feeder 1902 has been screwed onto or screwed into the flange 1942, the feed point 1902" and the portion of the feeder 1902 extending from the flange 1942 can be shortened or lengthened by rotating the flange 1942 accordingly. In other embodiments, feeder 1902 may be pre-threaded with mating threads for engagement with flange 1942 in order to improve ease of engaging the feeder with flange 1942. In yet another embodiment, feeder 1902 may have a smooth surface, and the hole 1946 of the flange 1942 may be unthreaded. In this embodiment, the hole 1946 may have a diameter similar to that of the feeder wire 1902, such as so that the engagement of the feeder wire 1902 is held in place by friction.

For alignment purposes, the flange 1942 may further include a threaded hole 1944 with two or more alignment holes 1947 that may be used for alignment to complementary alignment pins 1949 of the waveguide system 1948 , which in turn aids in aligning the hole 1944' of the waveguide system 1948 with the threaded hole 1944 of the flange 1942 (see FIGS. 19K-19L ). Once flange 1942 has been aligned with waveguide system 1948, flange 1942 and waveguide system 1948 may be secured to each other with threaded screws 1950, resulting in the complete assembly depicted in Figure 19L. In a threaded design, the feed point 1902" of the feed line 1902 can be adjusted inwards or outwards with respect to the waveguide system 1948 port 1945 from which electromagnetic waves are exchanged. The gap 1943 can be increased or decreased. The adjustments can be used to tune the coupling interface between the waveguide system 1948 and the feed point 1902″ of the feeder 1902. FIG. 19L also shows how the flange 1942 can be used to connect the feeder 1902 to the The retained coaxially aligned dielectric foam segments 1951 are aligned. The illustration in Figure 19L is similar to the transmission medium 1800' illustrated in Figure 18K. To complete the assembly process, the flange 1942 can be coupled to the waveguide system 1948, As depicted in Figure 19L.

Turning now to FIG. 19N , shown is a block diagram of an example non-limiting embodiment of a dielectric antenna 1901 ′ in accordance with various aspects described herein. Figure 19N depicts an array of pyramidal dielectric horn antennas 1901 ', each antenna having a corresponding aperture 1903'. Each antenna in the pyramidal dielectric horn antenna 1901' array can have a feed line 1902 with a respective feed point 1902" coupled to each respective core 1852 of the plurality of cables 1850. Each cable 1850 can be coupled to A different (or the same) waveguide system 1865', as shown in Figure 18T. An array of pyramidal dielectric horn antennas 1901 ' can be used to transmit wireless signals with multiple spatial orientations. A pyramidal dielectric horn antenna covering 360 degrees The 1901' array may enable one or more waveguide systems 1865' coupled to these antennas to perform omni-directional communication with other similar types of communication devices or antennas.

The bi-directional propagating properties of electromagnetic waves previously described with respect to dielectric antenna 1901 of FIG. 19A apply equally to electromagnetic waves propagating from core 1852 to feed point 1902", guided by feed line 1902 to aperture 1903' of pyramidal dielectric horn antenna 1901', and Applicable in the opposite direction. Similarly, the pyramidal dielectric horn antenna 1901 ' array can be substantially free or completely free of conductive outer surfaces and inner conductive material as discussed above. For example, in some embodiments, the pyramidal dielectric horn antenna The array of antennas 1901' and their corresponding feed points 1902' may be constructed of only dielectric materials such as polyethylene or polyurethane materials, or be constructed with only a small amount of conductive material that does not significantly alter the radiation pattern of the antennas.

It should be further noted that each antenna of the array of pyramidal dielectric horn antennas 1901' may have similar gain and electric field strength plots as shown for dielectric antenna 1901 in Figure 19B. As previously described for the dielectric antenna 1901 of FIG. 19A, each antenna of the pyramidal dielectric horn antenna 1901' array can also be used to receive wireless signals. In some embodiments, a single instance of a pyramidal dielectric horn antenna may be used. Similarly, multiple instances of the dielectric antenna 1901 of Figure 19A may be used in an array configuration similar to that shown in Figure 19N.

Turning now to FIG. 190 , shown is a block diagram of an example non-limiting embodiment of an array 1976 of dielectric antennas 1901 configurable for directing wireless signals in accordance with various aspects described herein. Array 1976 of dielectric antennas 1901 may be conical antennas 1901 or pyramidal dielectric antennas 1901'. To perform beam steering, the waveguide system coupled to the array 1976 of dielectric antennas 1901 can be adapted to utilize circuitry 1972 including amplifiers 1973 and phase shifters 1974, each pair coupled to a pair of dielectric antennas 1901 in the array 1976. One. By incrementally increasing the phase delay of the signal provided to the dielectric antenna 1901, the waveguide system can steer the far-field wireless signal from left to right (west to east).

For example, a waveguide system may provide a first signal to a dielectric antenna of column 1 ("C1") without a phase delay. The waveguide system may further provide column 2 ("C2") with a second signal comprising the first signal with the first phase delay. The waveguide system may further provide a third signal to the dielectric antenna of column 3 ("C3"), the third signal comprising the second signal having a second phase delay. Finally, the waveguide system can provide a fourth signal to the dielectric antenna of column 4 ("C4"), the fourth signal including the third signal with a third phase delay. These phase-shifted signals will shift the far-field wireless signals generated by the array from left to right. Similarly, right to left (east to west) ("C4" to C1), north to south ("R1" to "R4"), south to north ("R4" to "R1" ), and steers the far-field signal from southwest to northeast (“C1-R4” to “C4-R1”).

Using a similar technique, beam steering can also be performed in other directions (such as from southwest to northeast) by configuring the waveguide system to incrementally increase the phase of the signal transmitted by the following antenna sequence: "C1-R4", "C1- R3/C2-R4", "C1-R2/C2-R3/C3-R4", "C1-R1/C2-R2/C3-R3/C4-R4", "C2-R1/C3-R2/C4- R3", "C3-R1/C4-R2", "C4-R1". In a similar manner, beam steering can be performed from northeast to southwest, northwest to southeast, southeast to northwest, and other directions in three-dimensional space. Beam steering can be used, among other things, to align the array 1976 of dielectric antennas 1901 with remote receivers and/or to direct signals to mobile communication devices. In some embodiments, the phased array 1976 of dielectric antennas 1901 may also be used to circumvent the use of the gimbal assembly of FIG. 19M or other actuation mounts. Although beam steering controlled by phase delay has been described above, gain and phase adjustments can also be applied in a similar manner to the dielectric antenna 1901 of the phased array 1976 to provide additional control and versatility in forming the desired beam pattern.

Turning now to FIGS. 19P1-19P8 , shown are side block diagrams of exemplary non-limiting embodiments of a cable, flange, and dielectric antenna assembly in accordance with various aspects described herein. FIG. 19P1 depicts a cable 1850 that includes a transmission core 1852 as described earlier. As depicted in transmission media 1800, 1820, 1830, 1836, 1841, and/or 1843 of FIGS. 18A-18D and FIGS. 1832, core 1842 or hollow core 1842'. The cable 1850 may further include a housing (such as a dielectric housing) covered by an outer jacket as shown in FIGS. 18A-18C . In some embodiments, the outer sheath can be non-conductive (eg, polyethylene or equivalent). In other embodiments, the outer jacket may be a conductive shield that reduces leakage of electromagnetic waves propagating along the transmission core 1852 .

In some embodiments, one end of transmission core 1852 may be coupled to flange 1942 as previously described with respect to FIGS. 19J-19L . As noted above, the flange 1942 may align the transmission core 1852 of the cable 1850 with the feed point 1902 of the dielectric antenna 1901 . In some embodiments, feed point 1902 may be constructed of the same material as transmission core 1852 . For example, in one embodiment, transmission core 1852 may comprise a dielectric core, and feed point 1902 may likewise comprise a dielectric material. In this embodiment, the dielectric constants of the transmission core 1852 and the feed point 1902 may be similar or may differ by some controlled amount. The difference in dielectric constant can be controlled to tune the interface between transmission core 1852 and feed point 1902 for switching electromagnetic waves propagating therebetween. In other embodiments, transmission core 1852 may have a different configuration than feed point 1902 . For example, in one embodiment, transmission core 1852 may comprise an insulated conductor while feed point 1902 comprises a dielectric material without conductive material.

As shown in Figure 19J, the transmission core 1852 may be coupled to the flange 1942 via a central hole 1946, although in other embodiments, it will be appreciated that such a hole may also be off-center. In one embodiment, the bore 1946 can be threaded and the delivery core 1852 can have a smooth surface. In this embodiment, by inserting a portion of transfer core 1852 into bore 1946 and rotating flange 1942 , flange 1942 may engage transfer core 1852 to serve as a mold for forming complementary threads on the outer surface of transfer core 1852 . Once transfer core 1852 has been threaded onto or screwed into flange 1942, a portion of transfer core 1852 extending from flange 1942 may be shortened or lengthened by rotating flange 1942 accordingly.

In other embodiments, the transfer core 1852 may be pre-threaded with mating threads for engagement with the bore 1946 of the flange 1942 to improve ease of engaging the transfer core 1852 with the flange 1942 . In yet another embodiment, the transfer core 1852 can have a smooth surface, and the bore 1946 of the flange 1942 can be unthreaded. In this embodiment, the bore 1946 may have a diameter similar to that of the transmission core 1852, such as so that the engagement of the transmission core 1852 is held in place by friction. It will be appreciated that there are several other ways to engage the transmission core 1852 with the flange 1942, including various clips, fusions, compression fittings, and the like. The feed point 1902 of the dielectric antenna 1901 may engage the other side of the hole 1946 of the flange 1942 in the same manner as described for the transmission core 1852 .

There may be a gap 1943 between the transmission core 1852 and the feed point 1902 . However, in one embodiment, the gap 1943 can be adjusted by rotating the feed point 1902 while the transmission core 1852 is held in place (or vice versa). In some embodiments, the ends of the transmission core 1852 and the feed point 1902 that engage the flange 1942 may be adjusted so that they touch, thereby removing the void 1943 . In other embodiments, the end of the transmission core 1852 or the feed point 1902 that engages the flange 1942 may be intentionally tuned to create a particular gap size. The adjustability of the gap 1943 may provide an additional degree of freedom for adjusting the interface between the transmission core 1852 and the feed point 1902 .

Although not shown in Figures 19P1-19P8, another flange 1942 and similar coupling techniques may be utilized to couple the opposite end of the transmission core 1852 of the cable 1850 to a waveguide device such as that depicted in Figures 18S and 18T. A waveguide device may be used to transmit and receive electromagnetic waves along the transmission core 1852 . Depending on the operating parameters of the electromagnetic wave (e.g., operating frequency, wave mode, etc.), the electromagnetic wave can be transmitted within the transmission core 1852, on the outer surface of the transmission core 1852, or partially within the transmission core 1852 and the outer surface of the transmission core 1852. spread. When the waveguide device is configured as a transmitter, the signal generated by it induces an electromagnetic wave that propagates along the transmission core 1852 and transitions to the feed point 1902 at the junction between the transmitter and the feed point. The electromagnetic wave then propagates from the feed point 1902 into the dielectric antenna 1901 where it becomes a wireless signal at the aperture 1903 of the dielectric antenna 1901 .

Frame 1982 may be used to surround all or at least most of the outer surface of dielectric antenna 1901 (except aperture 1903) to improve transmission or reception of electromagnetic waves and/or reduce leakage of electromagnetic waves as they propagate toward aperture 1903. In some embodiments, a portion 1984 of the frame 1982 may extend to the feed point 1902 as shown in FIG. 19P2 to prevent leakage on the outer surface of the feed point 1902 . For example, the frame 1982 may be composed of a material (eg, a conductive material or a carbon material) that reduces leakage of electromagnetic waves. The shape of the frame 1982 may vary based on the shape of the dielectric antenna 1901 . For example, frame 1852 may have a flared straight face shape as shown in FIGS. 19P1-19P4 . Alternatively, frame 1852 may have a flared parabolic shape as shown in Figures 19P5-19P8. It will be appreciated that frame 1852 may have other shapes.

Aperture 1903 can have different shapes and sizes. In one embodiment, for example, aperture 1903 may utilize lenses having convex structures 1983 of various sizes as shown in FIGS. 19P1 , 19P4 , and 19P6-19P8 . In other embodiments, the aperture 1903 may have flat structures 1985 of various sizes as shown in Figures 19P2 and 19P5. In yet other embodiments, the aperture 1903 may utilize a lens having a pyramidal structure 1986 as shown in FIGS. 19P3 and 19Q1 . The lens of aperture 1903 may be an integral part of dielectric antenna 1901 or may be a component coupled to dielectric antenna 1901 as shown in Figure 19C. Additionally, the lens of aperture 1903 may be constructed from the same or different materials as dielectric antenna 1901 . Also, in some embodiments, the aperture 1903 of the dielectric antenna 1901 may extend outside the frame 1982 as shown in FIGS. 19P7-19P8 or may be confined within the frame 1982 as shown in FIGS. 19P1-19P6 .

In one embodiment, the dielectric constant of the lens of aperture 1903 as shown in FIGS. 19P1-19P8 may be configured to be substantially similar or different from the dielectric constant of dielectric antenna 1901 . Additionally, one or more interior portions of dielectric antenna 1901 (such as section 1986 of FIG. 19P4 ) may have a different dielectric constant than the rest of the dielectric antenna. The surface of the lens of the aperture 1903 as shown in FIGS. 19P1 to 19P8 may have a smooth surface or may have ridges such as shown in FIG. 19E to reduce surface reflection of electromagnetic waves as previously described.

Depending on the shape of the dielectric antenna 1901, the frame 1982 may have a different shape or size as shown in the front views as depicted in Figures 19Q1, 19Q2 and 19Q3. For example, frame 1982 may have a pyramid shape as shown in FIG. 19Q1 . In other embodiments, frame 1982 may have a circular shape as depicted in FIG. 19Q2 . In yet other embodiments, the frame 1982 may have an oval shape as depicted in FIG. 19Q3 .

The embodiments of FIGS. 19P1 - 19P8 and 19Q1 - 19Q3 may be combined in whole or in part with each other to create other embodiments contemplated by the subject disclosure. Additionally, the embodiments of FIGS. 19P1 - 19P8 and 19Q1 - 19Q3 may be combined with other embodiments of the subject disclosure. For example, the multi-antenna assembly of FIG. 20F may be adapted to utilize any of the embodiments of FIGS. 19P1-19P8 and 19Q1-19Q3. Additionally, multiple instances of a multi-antenna assembly adapted to utilize one of the embodiments of FIGS. 19P1-19P8 , 19Q1-19Q3 may be stacked on top of each other to form a phased array of phased arrays. In other embodiments, as shown in FIG. 191 , an absorbing sheet 1932 can be added to the dielectric antenna 1901 to control the width of near-field and far-field signals. Other combinations of the embodiments of FIGS. 19P1-19P8 and 19Q1-19Q3 with embodiments of the subject disclosure are contemplated.

Turning now to FIGS. 20A and 20B , there is illustrated a block diagram of an example non-limiting embodiment of a cable 1850 of FIG. 18A for inducing guided electromagnetic waves on a power line supported by a utility pole. In one embodiment, as depicted in FIG. 20A , a cable 1850 may be coupled at one end to a microwave device utilizing a hollow waveguide 1808 such as that shown in FIGS. 18A-18C at one or more ends of the cable 1850 A guided electromagnetic wave is emitted in an inner layer. The microwave device may transmit or receive signals from the cable 1850 using a microwave transceiver as shown in FIG. 10A. Guided electromagnetic waves induced in the one or more inner layers of the cable 1850 may propagate to exposed stubs of the cable 1850 within the horn antenna (shown in dashed lines in FIG. 20A ) for radiation via the horn antenna electromagnetic waves. The radiated signal from the horn antenna can in turn induce guided electromagnetic waves propagating longitudinally on power lines such as medium voltage (MV) power lines. In one embodiment, the microwave device may receive AC power from a low voltage (eg, 220V) power line. Alternatively, as shown in Figure 20B, the horn antenna can be replaced with a stub antenna to induce guided electromagnetic waves propagating longitudinally on power lines such as MV power lines or to transmit wireless signals to other antenna systems.

In an alternative embodiment, the hollow horn antenna shown in FIG. 20A may be replaced with a solid dielectric antenna, such as dielectric antenna 1901 of FIG. 19A or pyramidal horn antenna 1901' of FIG. 19N. In this embodiment, the horn antenna may radiate wireless signals that are directed to another horn antenna, such as bi-directional horn antenna 2040 shown in FIG. 20C. In this embodiment, each horn antenna 2040 can transmit wireless signals to or receive wireless signals from the other horn antenna 2040, as shown in FIG. 20C. This arrangement can be used to perform two-way wireless communication between the antennas. Although not shown, the horn antenna 2040 may be configured with an electromechanical device for directing the direction of the horn antenna 2040 .

In an alternative embodiment, the first cable 1850A' and the second cable 1850B' may be coupled to a microwave device and a transformer 2052, respectively, as shown in Figures 20A and 20B. First cable 1850A' and second cable 1850B' may be represented by, for example, cable 1820 or cable 1830 of FIGS. 18B and 18C , respectively, each cable having a conductive core. A first end of the conductive core of the first cable 1850A' may be coupled to a microwave device for propagating guided electromagnetic waves emitted therein. The second end of the conductive core of the first cable 1850A′ may be coupled to the first end of the conductive coil of the transformer 2052 for receiving guided electromagnetic waves propagating in the first cable 1850A′ and for passing through the conductive coil of the transformer 2052. The second end provides signals associated with the electromagnetic waves to the first end of the second cable 1850B'. The second end of the second cable 1850B' may be coupled to the horn antenna of FIG. 20A or may be exposed as a stub antenna of FIG. 20B for inducing guided electromagnetic waves propagating longitudinally on the MV power line.

In embodiments where cables 1850, 1850A' and 1850B' each include multiple instances 1800, 1820 and/or 1830 of transmission media, a multi-rod structure of antenna 1855 may be formed, as shown in Figure 18K. For example, each antenna 1855 may be coupled to a horn antenna assembly as shown in Figure 20A, or a pie pan antenna assembly (not shown) for radiating multiple wireless signals. Alternatively, antenna 1855 may be used as a stub antenna in FIG. 20B. The microwave apparatus of FIGS. 20A-20B may be configured to direct electromagnetic waves to beam-steer wireless signals transmitted by antenna 1855 . One or more of the antennas 1855 may also be used to induce guided electromagnetic waves on the power lines.

Turning now to FIG. 20C , shown is a block diagram of an example non-limiting embodiment of a communication network 2000 in accordance with various aspects described herein. In one embodiment, for example, waveguide system 1602 of Figure 16A may be incorporated into a network interface device (NID), such as NIDs 2010 and 2020 of Figure 20C. A NID with the functionality of a waveguide system 1602 can be used to enhance the transmission capability between a customer premise 2002 (business or residential) and a base frame 2004 (sometimes called a service area interface or SAI).

In one embodiment, central office 2030 may provide one or more fiber optic cables 2026 to base frame 2004 . Fiber optic cable 2026 may provide high-speed full-duplex data service (eg, 1 Gbps to 100 Gbps or higher) to micro-DSLAM 2024 located in pedestal 2004 . These data services may be used to deliver voice, Internet traffic, media content services (eg, streaming video services, broadcast television), and the like. In prior art systems, the mini-DSLAM 2024 is typically connected to twisted-pair telephone wires (e.g., Category 5e unshielded twisted-pair wire enclosed by an outer insulating jacket contained in a bundle comprising an unshielded twisted-pair cable ( UTP) cables, such as 24 gauge insulated solid conductors), the twisted-pair telephone wires are then directly connected to the customer terminal 2002. In such systems, the DSL data rate tapers off at 100 Mbps or less, due in part to factors such as the length of the traditional twisted pair cable to the customer terminal 2002.

However, the embodiment of Figure 20C differs from prior art DSL systems. In the illustration of FIG. 20C , for example, micro-DSLAM 2024 may be configured to be connected via cable 1850 (which may represent in whole or in part, singly or in combination, the cables described with respect to FIGS. 18A-18D and 18F-18L ). any one of the embodiments) to NID 2020. Utilizing the cable 1850 between the client terminal 2002 and the pedestal 2004 enables the NIDs 2010 and 2020 to transmit and receive guided electromagnetic waves for uplink and downlink communications. Based on the previously described embodiments, cable 1850 may be exposed to rain, or may be buried without adversely affecting electromagnetic wave propagation in either the downlink path or the uplink path, as long as the electric field profile of such waves in either direction At least partially or fully confined within the inner layer of the cable 1850 . In this illustration, downlink communication represents the communication path from the pedestal 2004 to the client terminal 2002 , while uplink communication represents the communication path from the client terminal 2002 to the pedestal 2004 . In embodiments where cable 1850 comprises one of the embodiments of FIGS. 18G-18H , cable 1850 may also be used for the purpose of powering NIDs 2010 and 2020 and other equipment of client terminal 2002 and pedestal 2004 .

In the client terminal 2002, the DSL signal may originate from a DSL modem 2006 (which may have a built-in router and which may provide wireless services such as WiFi to user equipment shown in the client terminal 2002). The DSL signal may be provided to the NID 2010 through the twisted pair telephone 2008 . NID 2010 may utilize integrated waveguide 1602 to transmit guided electromagnetic waves 2014 within cable 1850 that are directed to pedestal 2004 on an uplink path. In the downlink path, the DSL signal generated by micro-DSLAM 2024 may flow over twisted pair telephone line 2022 to NID 2020 . The waveguide system 1602 integrated in the NID 2020 can convert the DSL signal, or a portion thereof, from an electrical signal to guided electromagnetic waves 2014 that propagate within the cable 1850 on the downlink path. To provide full-duplex communication, the pilot electromagnetic waves 2014 on the uplink may be configured to operate at a different carrier frequency and/or different modulation than the pilot electromagnetic waves 2014 on the downlink in order to reduce or avoid interference . Additionally, as previously described, guided electromagnetic waves 2014 are guided by the core section of cable 1850 on both the uplink and downlink paths, and such waves may be configured to have the ability to confine guided electromagnetic waves in whole or in part to Field intensity profile in the inner layer of cable 1850. Although guided electromagnetic waves 2014 are shown outside cable 1850, these waves are depicted for illustrative purposes only. For this reason, the guided electromagnetic wave 2014 is drawn with a "hash mark" to indicate that it is guided by the inner layer of the cable 1850 .

On the downlink path, the integrated waveguide system 1602 of the NID 2010 receives the guided electromagnetic wave 2014 generated by the NID 2020 and converts it back into a DSL signal conforming to the requirements of the DSL modem 2006 . The DSL signal is then provided via a set of twisted pair telephone lines 2008 to a DSL modem 2006 for processing. Similarly, on the uplink path, the integrated waveguide system 1602 of the NID 2020 receives the guided electromagnetic wave 2014 generated by the NID 2010 and converts it back into a DSL signal conforming to the micro DSLAM 2024 requirements. The DSL signal is then provided via a set of twisted pair telephone lines 2022 to a micro-DSLAM 2024 for processing. Due to the relatively short lengths of telephone lines 2008 and 2022, DSL modem 2006 and micro-DSLAM 2024 can transmit and receive messages between themselves at very high speeds (e.g., 1 Gbps to 60 Gbps or more) on the uplink and downlink. Receive DSL signal. Consequently, the uplink and downlink paths can in most cases exceed the data rate limitations of traditional DSL communications over twisted pair telephone lines.

Typically, DSL equipment is configured for asymmetric data rates, since the downlink path usually supports higher data rates than the uplink path. However, cable 1850 can provide much higher speeds on both the downlink and uplink paths. Through a firmware update, a legacy DSL modem 2006 such as that shown in Figure 20C can be configured with higher speeds on both the uplink and downlink paths. Similar firmware updates can be made to the micro-DSLAM 2024 to take advantage of higher speeds on the uplink and downlink paths. Since the interface to the DSL modem 2006 and the mini-DSLAM 2024 remains a traditional twisted pair telephone line, for either the legacy DSL modem or the traditional mini-DSLAM, except for firmware changes and the addition of NIDs 2010 and 2020 to perform the transition from the DSL signal to the guided electromagnetic wave 2014 Other than the conversion of , and vice versa, no hardware changes are required. The use of NIDs enables the reuse of legacy modems 2006 and micro-DSLAMs 2024, which in turn can significantly reduce installation costs and system upgrades. For new configurations, newer versions of miniature DSLAMs and DSL modems can be configured with integrated waveguide systems to perform the above functions, thereby eliminating the need for the NID 2010 and 2020 with integrated waveguide systems. In this embodiment, the updated version of the modem 2006 and the updated version of the micro-DSLAM 2024 would connect directly to the cable 1850 and communicate via bi-directional guided electromagnetic wave transmission, thereby avoiding the need to use twisted pair telephone lines 2008 and 2022 to transmit or Required to receive DSL signals.

In embodiments where it is logically impractical or expensive to use the cable 1850 between the pedestal 2004 and the customer terminal 2002, the NID 2010 may be configured to instead be coupled to the waveguide 108 originating on the utility pole 118 and arriving at the customer terminal 2002 The NID 2010 of the terminal 2002 may have previously been buried in a cable 1850' in soil (similar to the cable 1850 of the subject disclosure). Cable 1850' may be used to receive and transmit guided electromagnetic waves 2014' between NID 2010 and waveguide 108. Waveguide 108 may be connected via waveguide 106 , which may be coupled to base station 104 . Base station 104 may provide data communication services to client terminals 2002 through its connection to central office 2030 over optical fiber 2026'. Similarly, where access from central office 2030 to pedestal 2004 is impractical over a fiber optic link but is possible via fiber optic link 2026′ to base station 104, an alternate path can be used via Cable 1850" (similar to cable 1850 of the subject disclosure) connects to NID 2020 of pedestal 2004. Cable 1850" may also be buried before it reaches NID 2020.

Turning now to FIGS. 20D-20F , shown are block diagrams of example non-limiting embodiments of antenna mounts that may be used in the communication network 2000 of FIG. 20C (or other suitable communication network) in accordance with various aspects described herein. In some embodiments, as depicted in FIG. 20D , the antenna mount 2053 may be coupled to a medium voltage power line through an inductive power supply that supplies energy to one or more waveguides integrated in the antenna mount 2053 system (not shown). Antenna mount 2053 may include an array of dielectric antennas 1901 (eg, 16 antennas), as shown in the top and side views depicted in Figure 20F. The dielectric antenna 1901 shown in FIG. 2OF can be as small in size as illustrated in the photographic comparison between sets of dielectric antennas 1901 and a conventional ballpoint pen. In other embodiments, a pole mounted antenna 2054 may be used as depicted in Figure 20D. In yet another embodiment, the antenna mount 2056 can be attached to a pole with an arm assembly, as shown in Figure 20E. In other embodiments, the antenna mount 2058 depicted in FIG. 20E may be placed on the top portion of the pole coupled to a cable 1850 such as that described in the subject disclosure.

The array of dielectric antennas 1901 in any of the antenna mounts of FIGS. 20D-20E may include one or more waveguide systems as described with respect to FIGS. 1-20 in the subject disclosure. The waveguide system may be configured to perform beam steering (for transmitting and receiving wireless signals) with an array of dielectric antennas 1901 . Alternatively, each dielectric antenna 1901 may serve as a separate sector for receiving and transmitting wireless signals. In other embodiments, the one or more waveguide systems integrated in the antenna mounts of FIGS. 20D-20E can be configured for use in a variety of multiple-input multiple-output (MIMO) transmit and receive technologies. A combination of dielectric antennas 1901 is used in this example. The one or more waveguide systems integrated in the antenna mounts of FIGS. 20D to 20E may also be configured to combine signals such as SISO, SIMO, MISO, SISO, signal diversity (e.g., frequency, time, space, polarization or other forms of signal diversity techniques) to any combination of dielectric antennas 1901 in any of the antenna mounts of FIGS. 20D to 20E . In yet another embodiment, the antenna mounts of FIGS. 20D-20E can be adapted to two or more stacks of the antenna array shown in FIG. 20F .

21A-21B describe embodiments for downlink communications and uplink communications. The method 2100 of FIG. 21A may begin at step 2102, in which an electrical signal (e.g., a DSL signal) is generated by a DSLAM (e.g., a micro-DSLAM 2024 of the pedestal 2004 or from a central office 2030), which is generated in step Converted at 2104 by the NID 2020 to guided electromagnetic waves 2014 and propagated on a transmission medium (such as cable 1850 ) to provide downlink services to client terminals 2002 . At step 2108, the NID 2010 of the customer terminal 2002 converts the guided electromagnetic wave 2014 back into an electrical signal (e.g., a DSL signal), which is provided at step 2110 over the telephone line 2008 to customer terminal equipment (CPE), such as a DSL Modem 2006. Alternatively or in combination, as an alternative or additional downlink (and/or uplink) path, power and/or guided electromagnetic waves 2014' may be routed from the utility grid's power line 1850' (with The inner waveguide illustrated in FIG. 18H ) is supplied to the NID 2010.

At step 2122 of method 2120 of FIG. 21B , DSL modem 2006 may provide an electrical signal (e.g., a DSL signal) via telephone line 2008 to NID 2010, which in turn converts the DSL signal over cable 1850 to a directed signal at step 2124. Guiding Electromagnetic Waves to NID 2020. At step 2128, NID 2020 of terminal 2004 (or central office 2030) converts pilot electromagnetic wave 2014 back to an electrical signal (eg, a DSL signal), which is provided to a DSLAM (eg, micro-DSLAM 2024) at step 2129. Alternatively or in combination, as an alternative or additional uplink (and/or downlink) path, the power and pilot electromagnetic wave 2014' can be routed from the utility grid's power line 1850' (as shown in Figure 18G or Figure 18H The inner waveguide shown in ) is supplied to the NID 2020.

Turning now to FIG. 21C , there is shown a flowchart illustrating an example non-limiting embodiment of a method 2130 for inducing and receiving electromagnetic waves on a transmission medium. At step 2132, the waveguides 1865 and 1865' of FIGS. 18N-18T may be configured to generate a first electromagnetic wave from a first communication signal (e.g., provided by a communication device such as a base station), and at step 2134 transmit A first electromagnetic wave having "only" the fundamental mode is induced at the interface of the medium. In an embodiment, the interface may be the outer surface of the transmission medium as depicted in Figures 18Q and 18R. In another embodiment, the interface may be an inner layer of the transmission medium as depicted in Figures 18S and 18T. At step 2136, waveguides 1865 and 1865' of FIGS. 18N-18T may be configured to receive a second electromagnetic wave at an interface of the same or a different transmission medium as described in FIG. 21C. In an embodiment, the second electromagnetic wave may have "only" the fundamental mode. In other embodiments, the second electromagnetic wave may have a combination of wave modes such as fundamental and non-fundamental modes. At step 2138, a second communication signal may be generated from the second electromagnetic wave for processing, eg, by the same or a different communication device. The embodiments of Figures 21C and 21D can be applied to any of the embodiments described in the subject disclosure.

Turning now to FIG. 21D , there is shown a flowchart illustrating an example non-limiting embodiment of a method 2140 for inducing and receiving electromagnetic waves on a transmission medium. At step 2142, the waveguides 1865 and 1865' of FIGS. 18N-18W may be configured to generate a first electromagnetic wave from a first communication signal (e.g., provided by a communication device), and at step 2144 at the interface of the transmission medium A second electromagnetic wave with "only" non-fundamental modes is induced at . In an embodiment, the interface may be the outer surface of the transmission medium as depicted in Figures 18Q and 18R. In another embodiment, the interface may be an inner layer of the transmission medium as depicted in Figures 18S and 18T. At step 2146, waveguides 1865 and 1865' of FIGS. 18N-18W may be configured to receive electromagnetic waves at an interface of the same or a different transmission medium as described in FIG. 21E. In an embodiment, electromagnetic waves may have "only" non-fundamental modes. In other embodiments, the electromagnetic waves may have a combination of wave modes such as fundamental and non-fundamental modes. At step 2148, a second communication signal may be generated from the electromagnetic waves for processing, eg, by the same or a different communication device. The embodiments of FIGS. 21E and 21F can be applied to any of the embodiments described in the subject disclosure.

FIG. 21E illustrates a flowchart of an example, non-limiting embodiment of a method 2150 for radiating a signal from a dielectric antenna, such as those shown in FIGS. 19A and 19N . Method 2150 may begin at step 2152, where a transmitter (such as waveguide system 1865' of FIG. 18T) generates a first electromagnetic wave comprising a first communication signal. At step 2153, the first electromagnetic wave in turn induces a second electromagnetic wave on the core 1852 of the cable 1850 coupled to the feed point of any of the dielectric antennas described in the subject disclosure. The second electromagnetic wave is received at the feed point at step 2154 and propagates to the proximal portion of the dielectric antenna at step 2155 . At step 2156, the second electromagnetic wave continues to propagate from the proximal portion of the dielectric antenna to the aperture of the antenna, and thereby causes the wireless signal to radiate at step 2157 as previously described with respect to FIGS. 19A-19N.

Figure 2 IF illustrates a flowchart of an example, non-limiting embodiment of a method 2160 for receiving a wireless signal at a dielectric antenna, such as the dielectric antenna of Figure 19A or Figure 19N. Method 2160 may begin at step 2161, in which a wireless signal is received by an aperture of a dielectric antenna. At step 2162, the wireless signal induces electromagnetic waves that propagate from the aperture to the feed point of the dielectric antenna. The electromagnetic wave, once received at the feed point at step 2163, propagates at step 2164 to the core of the cable coupled to the feed point. At step 2165, a receiver, such as waveguide system 1865' of FIG. 18T, receives the electromagnetic waves and at step 2166 generates a second communication signal from the electromagnetic waves.

Methods 2150 and 2160 may be used to adapt the dielectric antennas of Figures 19A, 19C, 19E, 19G-19I, and 19L-19O for use with other dielectric antennas, such as the dielectric antenna 2040 shown in Figure 20C. ) for two-way wireless communication, and/or for performing two-way communication with other communication devices such as portable communication devices (e.g., cell phones, tablets, laptops), wireless Wireless communication. A microwave device as shown in FIG. 20A may be configured with one or more cables 1850 coupled to a plurality of dielectric antennas 2040 as shown in FIG. 20C. In some embodiments, the dielectric antenna 2040 shown in FIG. 20C can be configured with more dielectric antennas (eg, 19C, 19E, 19G to 19I, and 19L to 19O) to further expand the wireless communication area of such antennas.

Methods 2150 and 2160 may further be adapted for use with phased array 1976 of dielectric antenna 1901 of FIG. 19O to steer transmitted far-field wireless signals by applying an incremental phase delay to a portion of the antenna. Methods 2150 and 2160 may also be adapted for adjusting the far-field wireless signal generated by dielectric antenna 1901 and/or the motion of dielectric antenna 1901 using the gimbal depicted in FIG. Oriented so as to improve reception of far-field wireless signals by a remote system, such as another dielectric antenna 1901 coupled to a waveguide system. Additionally, methods 2150 and 2160 may be adapted to receive instructions, messages or wireless signals from a remote system to enable the waveguide system to receive such signals through its dielectric antenna 1901 to perform adjustments to the far field signal.

Although the corresponding process is shown and described as a series of blocks in FIGS. Some blocks may occur in a different order and/or concurrently with other blocks than depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methodologies described below.

Figure 21G illustrates a flowchart of an example non-limiting embodiment of a method 2170 for detecting and mitigating disturbances occurring in a communication network such as, for example, the systems of Figures 16A and 16B. Method 2170 may begin at step 2172, where a network element, such as waveguide system 1602 of FIGS. deteriorating. Signal degradation may be detected based on any number of factors, including but not limited to: signal amplitude of the leading electromagnetic wave falling below a certain amplitude threshold, SNR falling below a certain signal-to-noise ratio (SNR) threshold, Quality of Service (QoS) falling below one or more thresholds, BER exceeding a certain Bit Error Rate (BER) threshold, PLR exceeding a certain Packet Loss Rate (PLR) threshold, reflected electromagnetic waves and forward Ratio of electromagnetic waves, unexpected changes or changes in wave patterns, spectral changes in guided electromagnetic waves that indicate that one or more objects are causing propagation loss or scattering of guided electromagnetic waves (e.g., accumulation of water on an outer surface of a transmission medium, splices in the transmission medium, broken branches, etc.), or any combination thereof. A sensing device, such as disturbance sensor 1604b of FIG. 16A, may be adapted to perform one or more of the signal measurements described above, and thereby determine whether the electromagnetic wave is experiencing signal degradation. The subject disclosure contemplates other sensing devices suitable for performing the measurements described above.

If signal degradation is detected at step 2174, the network element may proceed to step 2176, where the network element may determine which object or objects may be causing the degradation and, upon detection, forward to FIG. 16A The network management system 1601 to Figure 16B reports detected object(s). Object detection can be accomplished by spectral analysis or other forms of signal analysis, environmental analysis (e.g., air pressure readings, rain detection, etc.), or for detecting Other appropriate techniques for foreign bodies. For example, a network element may be configured to generate spectral data derived from electromagnetic waves received by the network element. The network element may then compare the spectral data to a plurality of spectral profiles stored in a memory of the network element. The plurality of spectral distribution curves may be pre-stored in the memory of the network element and may be used to characterize or identify obstructions which may cause propagation loss or Signal degradation.

For example, the accumulation of water (such as a thin layer of water and/or water droplets) on the outer surface of the transmission medium may cause signal degradation of the electromagnetic waves guided by the transmission medium, which can be determined by including the modeling of such obstructions. The spectral distribution curve of the spectral data is identified. When electromagnetic waves are received on the outer surface of a transmission medium that has been subjected to water (e.g., simulated rain), it is possible to collect and analyze the spectral data generated by the test equipment (e.g., a waveguide system with spectrum analysis capabilities) in a controlled The spectral distribution curves are generated in an environment such as a laboratory or other suitable test environment. Obstacles, such as water, may generate different spectral signatures than other obstacles (eg, splicing between transmission media). Unique spectral signatures can be used to identify obstacles relative to other obstacles. Using this technique, spectral distribution curves can be generated to characterize other obstacles such as fallen tree branches on the transmission medium, splicing, etc. In addition to spectral distribution curves, thresholds for different metrics such as SNR, BER, PLR, etc. can be generated. These thresholds may be selected by the service provider based on desired performance measurements of communication networks utilizing guided electromagnetic waves to communicate data. Some obstacles can also be detected by other methods. For example, rain may be detected by a rain detector coupled to the network element, a fallen tree branch may be detected by a vibration detector coupled to the network element, and so on.

If the network element cannot access the device to detect an object that may be causing electromagnetic wave degradation, the network element may skip step 2176 and proceed to step 2178, where the network element notifies the detected signal degradation to one or A plurality of adjacent network elements (eg, other waveguide system(s) 1602 in the vicinity of the network element). If signal degradation is significant, the network element may utilize a different medium for communicating with neighboring network element(s), such as eg wireless communication. Alternatively, network elements may significantly reduce the frequency of operation of the piloted electromagnetic wave (e.g., from 40 GHz to 1 GHz), or utilize other piloted electromagnetic waves operating at a lower frequency such as a control channel (e.g., 1 MHz) to communicate with neighboring networks. components to communicate. Low frequency control channels may be less susceptible to interference from object(s) that cause signal degradation at much higher operating frequencies.

Once an alternate means of communication is established between network elements, at step 2180, the network element and neighboring network elements may coordinate procedures for adjusting the guided electromagnetic waves to mitigate detected signal degradation. For example, the process may include a protocol for selecting which network elements will make adjustments to the electromagnetic waves, the frequency and magnitude of the adjustments, and goals to achieve desired signal quality (eg, QoS, BER, PLR, SNR, etc.). For example, if the object causing signal degradation is the accumulation of water on the outer surface of the transmission medium, the network elements may be configured to adjust the polarization of the electric (e-field) and/or magnetic (h-field) fields of the electromagnetic waves to achieve e Radial alignment of the fields, as shown in Figure 21H. Specifically, FIG. 21H presents a block diagram 2101 illustrating an example non-limiting embodiment of e-field alignment of electromagnetic waves for mitigating damage due to water accumulation on a transmission medium in accordance with various aspects described herein. caused by propagation loss. In this example, a longitudinal section of the cable, such as an insulated metal cable implementation of the transmission medium 125, is presented with field vectors illustrating the e-field associated with a guided electromagnetic wave propagating at 40 GHz. A stronger e-field is represented by a darker field vector than a weaker e-field.

In one embodiment, electromagnetic waves can be generated by specific wave modes such as transverse magnetic (TM) modes, transverse electric (TE) modes, transverse electromagnetic (TEM) modes, or a mixture of TM and TE modes (also referred to as for HE mode)) to achieve polarization adjustment. For example, assuming that the network element includes the waveguide system 1865' of FIG. 18W, the e-field can be achieved by configuring two or more MMICs 1870 to change the phase, frequency, amplitude, or combination thereof of the electromagnetic waves generated by each MMIC 1870. Polarization adjustment. For example, some adjustments may be such that the e-field in the region of the water film shown in Figure 21H is aligned vertically with the water surface. In the water film, the electric field perpendicular (or nearly perpendicular) to the water surface will induce a weaker current than the e-field parallel to the water film. By inducing a weaker current, longitudinally propagating electromagnetic waves will experience less propagation loss. In addition, the e-field is also expected to be concentrated to extend into the air above the water film. Propagation losses are also reduced if the e-field concentration in air is kept high and most of the total field strength is in air rather than being concentrated in the region of water and insulators. For example, even if the e-field could be perpendicular (or radially aligned) to the water film, an electromagnetic wave such as a Goubau wave (or a TM00 wave—see block 2131 of Figure 21K) that is tightly confined to an insulating layer will experience a higher e-field. The propagation loss of , because more field strength is concentrated in the region of water.

Therefore, an electromagnetic wave with an e-field that is perpendicular (or nearly perpendicular) to the water film and has a higher proportion of field strength in the air region (i.e. above the water film) will have a higher field strength than in the insulating layer or the water layer Electromagnetic waves that are tightly confined or that have an e-field in the direction of propagation within the water film region where higher losses are generated suffer less propagation loss.

Figure 21H depicts the e-field of a TM01 electromagnetic wave operating at 40 GHz in a longitudinal view of an insulated conductor. In contrast, Figures 21I and 21J depict cross-sectional views 2111 and 2121, respectively, of the insulated conductor of Figure 21H, which illustrate the field strength of the e-field in the direction of propagation of the electromagnetic wave (i.e. 21I and the e-field outside the page of Figure 21J). The electromagnetic waves shown in FIG. 21I and FIG. 21J have TM01 wave modes at 45 GHz and 40 GHz, respectively. FIG. 21I shows that the intensity of the e-field in the propagation direction of the electromagnetic wave is higher in the region between the outer surface of the insulator and the outer surface of the water film (ie, the water film region). High intensities are depicted with lighter colors (the lighter the color, the higher the intensity of the e-field pointing out of the page). Figure 21I illustrates that there is a high concentration of the e-field with longitudinal polarization in the water film region, which leads to high currents in the water film and thus high propagation losses. Therefore, electromagnetic waves at 45 GHz (with the TM01 wave mode) are less suitable in some cases for reducing rain or other obstructions located on the outer surface of an insulated conductor.

In contrast, FIG. 21J shows that the strength of the e-field in the propagation direction of the electromagnetic wave is weak in the water film region. Lower intensities are depicted by darker colors in the water film area. The lower strength is a result of the e-field being polarized mostly perpendicular or radial to the water film. As shown in Figure 21H, the radially aligned e-fields are also highly concentrated in the air region. Therefore, an electromagnetic wave at 40 GHz (with TM01 wave mode) induces less current in the water film than a 45 GHz wave with the same wave mode. Therefore, the electromagnetic wave of FIG. 21J exhibits properties more suitable for reducing propagation loss due to accumulation of water film or water droplets on the outer surface of an insulated conductor.

Since the physical properties of the transmission medium may vary, and the influence of water or other obstructions on the outer surface of the transmission medium may cause non-linear effects, it may not always be possible to accurately model all situations to achieve the first step in step 2182. e-field polarization and e-field concentration in air depicted in Figure 21H at one iteration. To increase the speed of the reduction process, the network element may be configured to select, at step 2186, a starting point for adjusting the electromagnetic waves from a look-up table. In one embodiment, the entries of the lookup table may be searched for a match to the type of object detected at step 2176 (eg, rainwater). In another embodiment, a look-up table may be searched for matches to spectral data derived from affected electromagnetic waves received by network elements. Table entries may provide specific parameters (eg, frequency, phase, amplitude, wave mode, etc.) for adjusting the electromagnetic waves to achieve at least a coarse adjustment that achieves e-field-like properties as shown in Figure 21H. Coarse tuning can be used to increase the likelihood of convergence on a solution that achieves the desired propagation properties discussed previously with respect to Figures 21H and 21J.

Once coarse adjustments have been made at step 2186, the network element may determine at step 2184 whether the adjustments have improved signal quality to a desired target. Step 2184 may be implemented through a cooperative exchange between network elements. For example, assume that the network element at step 2186 generates adjusted electromagnetic waves according to parameters obtained from the look-up table and transmits the adjusted electromagnetic waves to neighboring network elements. At step 2184, the network element may determine whether the adjustment has improved signal quality by receiving feedback from neighboring network elements that received the adjusted electromagnetic wave, analyzing the received wave's quality, and providing the result to a network element. Similarly, a network element may test the modulated electromagnetic waves received from a neighboring network element and may provide feedback to the neighboring network element including the results of the analysis. Although specific search algorithms are discussed above, other search algorithms may equally be employed, such as gradient search, genetic algorithm, global search, or other optimization techniques. Thus, steps 2182, 2186 and 2184 represent tuning and testing procedures performed by the network element and its neighbor(s).

With this in mind, if at step 2184 the network element (or its neighbors) determines that the signal quality has not achieved one or more desired parametric goals (e.g., SNR, BER, PLR, etc.), then at step 2182 the network element may and each of its neighbors begins to make incremental adjustments. At step 2182, the network element (and/or its neighbors) may be configured to incrementally adjust the amplitude, phase, frequency, wave pattern, and/or other tunable characteristics of the electromagnetic wave until the steering goal is achieved. To perform these adjustments, the network element (and its neighbors) may be configured with the waveguide system 1865' of Figure 18W. A network element (and its neighbors) may utilize two or more MMICs 1870 to incrementally adjust one or more operating parameters of electromagnetic waves to achieve e-fields polarized in specific directions (e.g., propagation in regions away from water films direction). The two or more MMICs 1870 may also be configured to incrementally adjust one or more operating parameters that achieve electromagnetic waves with highly concentrated e-fields in the air region (outside obstacles).

The iterative process may be a trial-and-error process coordinated between network elements to reduce the time to converge on a solution that improves both upstream and downstream communications. For example, as part of the coordination process, one network element may be configured to adjust the amplitude of electromagnetic waves but not the wave pattern, while another network element may be configured to adjust the wave pattern but not the amplitude. The number of iterations and adjustment combinations for achieving desired properties in electromagnetic waves to reduce obstructions on the outer surface of the transmission medium can be established and programmed into the network elements by the service provider based on experiments and/or simulations.

Once the network element(s) detects at step 2184 that the signal quality of the uplink and downlink electromagnetic waves has improved to a level desired to achieve one or more parametric goals (e.g., SNR, BER, PLR, etc.), the network element(s) may Proceed to step 2188 and restore communication based on the adjusted uplink and downlink electromagnetic waves. When communication occurs at step 2188, the network element may be configured to transmit an upstream test signal and a downstream test signal based on the raw electromagnetic wave in order to determine whether the signal quality of such wave has improved. These test signals may be transmitted at periodic intervals (eg, every 30 seconds or other suitable period). For example, each network element may analyze the spectral data of the received test signal to determine whether it achieves a desired spectral profile and/or other parametric goals (eg, SNR, BER, PLR, etc.). If the signal quality has not improved or has improved only marginally, the network element may be configured to continue communicating at step 2188 using the adjusted uplink electromagnetic waves and downlink electromagnetic waves.

However, if the signal quality has improved enough to return to utilizing the original electromagnetic wave, the network element(s) may proceed to step 2192 to restore the settings that generated the original electromagnetic wave (e.g., original wave pattern, original amplitude, original frequency, original phase , original spatial orientation, etc.). Signal quality may be improved due to the removal of obstacles (e.g., evaporation of rainwater, removal of fallen tree branches by field personnel, etc.). At step 2194, the network element may utilize raw electromagnetic waves to initiate communications and perform uplink and downlink tests. If the network element determines at step 2196 that the signal quality of the raw electromagnetic wave is satisfactory based on the tests performed at step 2194, the network element may resume communication using the raw electromagnetic wave and proceed to step 2172 and subsequent steps as previously described .

At step 2196, a successful test may be determined by analyzing the test signal according to parametric objectives (eg, BER, SNR, PLR, etc.) associated with the original electromagnetic wave. If at step 2196 it is determined that the test performed at step 2194 was successful, then the network element(s) may proceed to steps 2182, 2186 and 2184 as previously described. Since a previous adjustment of the uplink electromagnetic wave and the downlink electromagnetic wave may have been successfully determined, the network element(s) may restore the settings for the previously adjusted electromagnetic wave. Accordingly, a single iteration of any of steps 2182 , 2186 , and 2184 may be sufficient to return to step 2188 .

It should be noted that in some embodiments it may be desirable to restore the original electromagnetic waves if, for example, the data throughput is better when using the original electromagnetic waves than when using the adjusted electromagnetic waves. However, the network element(s) may alternatively be configured to continue from step 2188 when the data throughput at the adjusted electromagnetic wave is better or close to that of the original electromagnetic wave.

It should also be noted that while Figures 21H and 21K describe the TM01 wave mode, other wave modes (e.g., HE waves, TE waves, TEM waves, etc.) or combinations of wave modes can also achieve the desired wave pattern shown in Figure 21H. Effect. Thus, a wave mode alone or in combination with one or more other wave modes can generate electromagnetic waves with reduced propagation loss e-field properties as described with respect to Figures 21H and 21J. Therefore, such wave patterns are conceived as possible wave patterns that network elements can be configured to generate.

It should be further noted that method 2170 may be adapted to generate other wave modes at steps 2182 or 2186 that may not be subject to a cutoff frequency. For example, FIG. 21L depicts a block diagram 2141 of an example non-limiting embodiment of an electric field of a mixing wave in accordance with various aspects described herein. Waves with the HE mode have a linearly polarized e-field that is directed away from the direction of propagation of the electromagnetic wave and can be perpendicular (or nearly perpendicular) to the obstacle region (e.g., the water film shown in Figures 21H to 21J ). Waves with HE mode can be configured to generate an e-field extending substantially outside the outer surface of the insulated conductor, resulting in more total accumulated field strength in air. Therefore, some electromagnetic waves with HE modes can exhibit the properties of large wave modes with e-fields that are orthogonal or nearly orthogonal to the obstacle zone. As described earlier, this property can reduce propagation loss. Unlike other wave modes with non-zero cutoff frequencies, electromagnetic waves with HE modes also have the unique property that they do not have a cutoff frequency (ie, they can operate near DC).

Turning now to FIG. 21M , there is shown a block diagram 2151 illustrating an example non-limiting embodiment of the electric field characteristics of hybrid waves relative to Goubau waves in accordance with various aspects described herein. Diagram 2158 shows the energy distribution between the HE11 mode wave and the Goubau wave of an insulated conductor. The energy graph of the sketch 2158 assumes that the same amount of power was used to generate the Goubau wave as the HE11 wave (ie, the same area under the energy curve). In the illustration of sketch 2158, the Goubau wave has a sharp drop in power when it extends beyond the outer surface of the insulated conductor, whereas the HE11 wave has a rather small power drop outside the insulation. Therefore, Goubau waves have a higher energy concentration near the insulating layer than HE 11 waves. Sketch 2167 depicts a similar Goubau and HE11 energy curve when a water film is present on the outer surface of the insulator. The difference between the energy curves of schemes 2158 and 2167 is that the power drop of the Goubau and HE11 energy curves starts on the outer edge of the insulator of scheme 2158 and the outer edge of the water film of scheme 2167. However, energy graphs 2158 and 2167 depict the same behavior. That is, the electric field of the Goubau wave is tightly confined to the insulating layer, which when exposed to water leads to a larger propagation loss than the electric field of the HE11 wave with a higher concentration outside the insulating layer and water film. These properties are depicted in HE11 diagram 2168 and Goubau diagram 2159, respectively.

By adjusting the operating frequency of the HE11 wave, the e-field of the HE11 wave can be configured to extend above the thin water film, as shown in block diagram 2169 of FIG. The e-field has a greater accumulated field strength in the region of air than . Figure 21N depicts a wire having a radius of 1 cm and an insulation radius of 1.5 cm and a dielectric constant of 2.25. As the operating frequency of the HE11 wave decreases, the e-field extends outward, expanding the size of the wave mode. At certain operating frequencies (eg, 3 GHz), the wave mode spread can be significantly larger than the diameter of the insulated wire and any obstructions that may be present on the insulated wire.

By making the e-field perpendicular to the water film and putting most of its energy outside the water film, HE11 waves have smaller propagation loss than Goubau waves when the transmission medium is subjected to water or other obstacles. Although Goubau waves have the desired radial e-field, the wave is tightly coupled to the insulating layer, which results in a high concentration of the e-field in the obstacle region. Therefore, Goubau waves still suffer from high propagation loss when there are obstacles such as water films on the outer surface of the insulated conductor.

Turning now to FIGS. 22A and 22B , block diagrams illustrating an example non-limiting embodiment of a waveguide system 2200 for transmitting hybrid waves according to various aspects described herein are shown. The waveguide system 2200 may include a probe 2202 coupled to a slidable or rotatable mechanism 2204 that enables the probe 2202 to be placed in different positions or orientations relative to the outer surface of the insulated conductor 2208 . Mechanism 2204 may include a coaxial feed 2206 or other coupling capable of transmitting electromagnetic waves through probe 2202 . Coaxial feed 2206 may be placed at a location on mechanism 2204 such that the path difference between probes 2202 is half a wavelength or some odd multiple thereof. When the probe 2202 generates electromagnetic signals of opposite phases, electromagnetic waves may be induced on the outer surface of the insulated conductor 2208 having a mixed mode (eg, HE11 mode).

Mechanism 2204 may also be coupled to a motor or other actuator (not shown) to move probe 2202 to a desired position. In one embodiment, for example, waveguide system 2200 may include a controller that directs a motor to rotate probe 2202 (assuming it is rotatable) to different positions (e.g., east and west) in order to generate Electromagnetic waves in the HE11 mode shown in the block diagram 2300 of FIG. 23 are horizontally polarized. To guide electromagnetic waves onto the outer surface of the insulated conductor 2208, the waveguide system 2200 may further include a tapered horn 2210 as shown in FIG. 22B. Tapered horn 2210 may be coaxially aligned with insulated conductor 2208 . To reduce the cross-sectional size of tapered horn 2210 , an additional insulating layer (not shown) may be placed over insulated conductor 2208 . The additional insulating layer may be similar to the tapered insulating layer 1879 shown in Figures 18Q and 18R. The additional insulating layer may have a tapered end pointing away from the tapered horn 2210 . The tapered insulating layer 1879 may reduce the size of an initial electromagnetic wave emitted according to the HE11 mode. As the electromagnetic wave propagates towards the tapered end of the insulating layer, the HE11 mode expands until the electromagnetic wave reaches its full size, as shown in FIG. 23 . In other embodiments, waveguide system 2200 may not require the use of tapered insulating layer 1879 .

Figure 23 illustrates that the HE11 wave mode can be used to reduce obstructions such as rain. For example, as shown in FIG. 23 , assume that rainwater has caused a film of water to surround the outer surface of the insulated conductor 2208 . Assume further that water droplets have collected on the bottom of the insulated conductor 2208 . As illustrated in Figure 23, the water film accounts for a small fraction of the total HE11 wave. Also, by having the HE11 wave with horizontal polarization, the water droplet is in the lowest intensity region of the HE11 wave, thereby reducing the loss caused by the droplet. Thus, HE11 waves suffer from much lower propagation loss and thus greater energy in the region occupied by water than Goubau waves or waves with modes that are tightly coupled to the insulated conductor 2208 .

Applicants believe that the waveguide system 2200 of FIGS. 22A-22B may be replaced by other waveguide systems of the subject disclosure capable of generating electromagnetic waves having HE modes. For example, the waveguide system 1865' of Figure 18W can be configured to generate electromagnetic waves having an HE mode. In an embodiment, two or more MMICs 1870 of the waveguide system 1865' may be configured to generate electromagnetic waves of opposite phase to generate polarized e-fields, such as those present in the HE mode. In another embodiment, different pairs of MMICs 1870 can be selected to generate HE polarized at different spatial locations (e.g., north and south, west and east, northwest and southeast, northeast and southeast, or other sub-section coordinates). Wave. Additionally, the waveguide system of FIGS. 18N-18W may be configured to launch electromagnetic waves having an HE mode onto a core 1852 of one or more embodiments of a cable 1850 suitable for propagating HE mode waves.

Although HE waves may have desirable properties for reducing obstructions on transmission media, applicants believe that certain wave modes (e.g., TE modes, TM modes, TEM modes, or combinations thereof) with certain cut-off frequencies may also exhibit Waves that are large enough and have a polarization e-field that is normal (or nearly normal) to the obstacle zone, so that they can be used to mitigate propagation losses caused by obstacles. For example, at step 2086, method 2070 may be adapted to generate such a wave pattern from a lookup table. A polarized e-field having a certain cut-off frequency, exhibiting a wave mode, eg, larger than an obstacle, and perpendicular (or approximately perpendicular) to an obstacle may be determined by experimentation and/or simulation. Once the combination of parameters (e.g., amplitude, phase, frequency, wave mode(s), spatial location, etc.) for generating one or more waves with a cutoff frequency of low propagation loss properties is determined, the The parameterization results can then be stored in a look-up table in memory of the waveguide system. Similarly, wave modes with cutoff frequencies exhibiting reduced propagation loss properties may also be iteratively generated by any of the search algorithms previously described in the course of steps 2082 to 2084 .

Although the corresponding process is shown and described as a series of blocks in FIG. 21G for purposes of simplicity of illustration, it should be understood and appreciated that claimed subject matter is not limited by the order of the blocks, as some methods The blocks may occur in a different order and/or concurrently with other blocks than depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methodologies described below.

Figure 24 illustrates a flowchart of an example non-limiting embodiment of a method 2400 for transmitting and receiving electromagnetic waves. Method 2400 may be adapted for use with waveguide 2522 shown in FIGS. 25A-25C . Method 2400 can begin at step 2402, where a generator generates a first electromagnetic wave. At step 2404, the waveguide guides a first electromagnetic wave to the interface of the transmission medium, which in turn induces a second electromagnetic wave at the interface of the transmission medium at step 2406. Steps 2402 to 2406 may be applied to the waveguide 2522 of Figures 25A, 25B and 25C. The generator may be a MMIC 1870 or a slot 1863 as shown in Figures 18N-18W. For purposes of illustration only, assume that the generator is a MMIC 2524 positioned within a waveguide 2522 as shown in Figures 25A-25C. Although shown in Figures 25A-25C in longitudinal views of cylindrical waveguide 2522, waveguide 2522 may be adapted into other structural shapes (eg, square, rectangular, etc.).

Turning now to the illustration of FIG. 25A , a waveguide 2522 covers a first region 2506 of a core 2528 . Within first region 2506 , waveguide 2522 has an outer surface 2522A and an inner surface 2523 . The inner surface 2523 of the waveguide 2522 may be composed of a metallic material, carbon, or other material that reflects electromagnetic waves and thereby enables the waveguide 2522 to be configured at step 2404 to direct the first electromagnetic wave 2502 towards the core 2528 . Core 2528 may include a dielectric core extending to inner surface 2523 of waveguide 2522 (as described in the subject disclosure). In other embodiments, the dielectric core may be surrounded by a cladding (as shown in FIG. 18A ), whereby the cladding extends to the inner surface 2523 of the waveguide 2522 . In yet other embodiments, the core 2528 may comprise an insulated conductor in which the insulator extends to the inner surface 2523 of the waveguide 2522 . In this embodiment, the insulated conductor may be a power line, coaxial cable, or other type of insulated conductor.

In the first region 2506 , the core 2528 includes an interface 2526 for receiving the first electromagnetic wave 2502 . In one embodiment, interface 2526 of core 2528 may be configured to reduce reflection of first electromagnetic wave 2502 . In one embodiment, the interface 2526 may be a tapered structure for reducing reflection of the first electromagnetic wave 2502 from the surface of the core 2528 . Other structures can be used for interface 2526. For example, interface 2526 may taper in part with circular dots. Accordingly, the subject disclosure contemplates any structure, configuration, or adaptation of interface 2526 that can reduce reflection of first electromagnetic wave 2502 . At step 2406 , first electromagnetic wave 2502 induces (or otherwise generates) second electromagnetic wave 2504 that propagates within core 2528 in first region 2506 covered by waveguide 2522 . The inner surface 2523 of the waveguide 2522 confines the second electromagnetic wave 2504 within the core 2528 .

The second region 2508 of the core 2528 is not covered by the waveguide 2522 and is thus exposed to the environment (eg, air). In the second region 2508 , the second electromagnetic wave 2504 propagates outward from the discontinuity between the edge of the waveguide 2522 and the exposed core 2528 . To reduce radiation from said second electromagnetic wave 2504 into the environment, the core 2528 may be configured with a tapered structure 2520 . As the second electromagnetic wave 2504 propagates along the tapered structure 2520, the second electromagnetic wave 2504 remains substantially confined to the tapered structure 2520, thereby reducing radiation losses. The tapered structure 2520 ends at the transition from the second region 2508 to the third region 2510 . In the third zone, the core has a cylindrical structure 2529 having a diameter equal to the end point of the tapered structure 2520 at the junction between the second zone 2508 and the third zone 2510 . In the third region 2510 of the core 2528, the second electromagnetic wave 2504 experiences lower propagation loss. In one embodiment, this may be achieved by selecting the diameter of the core 2528 such that the second electromagnetic wave 2504 is loosely confined to the outer surface of the core 2528 in the third region 2510 . Alternatively or in combination, the propagation loss of the second electromagnetic wave 2504 may be reduced by configuring the MMIC 2524 to adjust the wave mode, wavelength, operating frequency, or other operating parameters of the first electromagnetic wave 2502 .

Figure 25D illustrates a portion of the waveguide 2522 of Figure 25A depicted as a cylindrical ring (which does not show the MMIC 2524 or tapered structure 2526 of Figure 25A). In the simulation, a first electromagnetic wave was injected at the end of the core 2528 shown in Figure 25D. The simulation assumes that there is no reflection of the first electromagnetic wave based on the assumption that the tapered structure 2526 (or other suitable structure) is used to reduce the reflection of the first electromagnetic wave. The simulation is shown as two longitudinal cross-sectional views of core 2528 partially covered by waveguide section 2523A, and an orthogonal cross-sectional view of core 2528 . In the case of a longitudinal cross-sectional view, one of the representations is an enlarged view of a part of the first representation.

As can be seen from the simulation, the electromagnetic wavefield 2532 of the second electromagnetic wave 2504 is confined within the core 2528 by the inner surface 2523 of the waveguide section 2523A. As the second electromagnetic wave 2504 enters the second region 2508 (no longer covered by the waveguide section 2523A), the tapered structure 2520 reduces the electromagnetic wavefield 2532 as it expands on the outer tapered surface of the core 2528 radiation loss. As the second electromagnetic wave 2504 enters the third region 2510, the electromagnetic wave field 2532 stabilizes and thereafter remains loosely coupled to the core 2528 (depicted in the longitudinal and orthogonal cross-sectional views), which reduces propagation loss.

FIG. 25B provides an alternate embodiment of a tapered structure 2520 in the second region 2508 . As depicted in FIG. 25B , core 2528 may be maintained by extending waveguide 2522 into second region 2508 with tapered structure 2522B and through first region 2506 , second region 2508 and third region 2510 of core 2528 diameter to avoid tapered structure 2520. The horn-shaped structure 2522B can be used to reduce the radiation loss of the second electromagnetic wave 2504 when the second electromagnetic wave 2504 transitions from the first region 2506 to the second region 2508 . In the third zone 2510, the core 2528 is exposed to the environment. As noted earlier, the core 2528 is configured in the third region 2510 to reduce the propagation loss of the second electromagnetic wave 2504 . In one embodiment, this may be achieved by selecting the diameter of the core 2528 such that the second electromagnetic wave 2504 is loosely confined to the outer surface of the core 2528 in the third region 2510 . Alternatively or in combination, the propagation loss of the second electromagnetic wave 2504 can be reduced by adjusting the wave mode, wavelength, operating frequency or other performance parameters of the first electromagnetic wave 2502 .

The waveguide 2522 of FIGS. 25A and 25B may also be adapted to receive electromagnetic waves. For example, waveguide 2522 of FIG. 25A may be adapted to receive electromagnetic waves at step 2412. This may be represented by electromagnetic wave 2504 propagating in third zone 2510 from east to west (the orientation shown at the bottom right of FIGS. 25A-25B ) towards second zone 2508 . After reaching the second region 2508 , the electromagnetic wave 2504 becomes progressively more tightly coupled to the tapered structure 2520 . When the electromagnetic wave reaches the boundary between the second region 2508 and the first region 2506 (ie, the edge of the waveguide 2522 ), the electromagnetic wave 2504 propagates within the core 2528 bounded by the inner surface 2523 of the waveguide 2522 . Eventually, the electromagnetic wave 2504 reaches the end of the tapered interface 2526 of the core 2528 and radiates as a new electromagnetic wave 2502 guided by the inner surface 2523 of the waveguide 2522 .

One or more antennas of the MMIC 2524 may be configured to receive the electromagnetic waves 2502, thereby converting the electromagnetic waves 2502 at step 2414 into electrical signals that may be processed by a processing device (eg, a receiver circuit and a microprocessor). To prevent interference between electromagnetic waves emitted by the MMIC 2524, the remote waveguide system emitting the electromagnetic waves 2504 received by the waveguide 2522 of FIG. Other adjustable operating parameters to transmit electromagnetic waves 2504 to avoid interference. Electromagnetic waves may be received by the waveguide 2522 of FIG. 25B in a similar manner as described above.

Turning now to FIG. 25C, the waveguide 2522 of FIG. 25B can be adapted to support a transmission medium 2528 having no endpoints as shown in FIG. 25C. In this illustration, waveguide 2522 includes cavity 2525 in first region 2506 of core 2528 . The cavity 2525 creates a void 2527 between the outer surface 2521 of the core 2528 and the inner surface 2523 of the waveguide 2522 . Void 2527 provides sufficient space for placing MMIC 2524 on inner surface 2523 of waveguide 2522 . To enable waveguide 2522 to receive electromagnetic waves from either direction, waveguide 2522 may be configured with symmetrical regions: 2508 and 2508', 2510 and 2510', and 2512 and 2512'. In the first region 2506, the cavity 2525 of the waveguide 2522 has two tapered structures 2522B' and 2522B". These tapered structures 2522B' and 2522B" allow electromagnetic waves to gradually enter from either direction of the core 2528. Or leave chamber 2525. MMIC 2524 may be configured with a directional antenna for emitting first electromagnetic waves 2502 directed from east to west or west to east with respect to a longitudinal view of core 2528 . Similarly, the directional antenna of MMIC 2524 may be configured to receive electromagnetic waves propagating longitudinally on core 2528 from east to west or from west to east. Depending on whether the directional antenna of the MMIC 2524 transmits from east to west or west to east, the process of transmitting electromagnetic waves is similar to that described for Figure 25B.

Although not shown, the waveguide 2522 of FIG. 25C can be configured with a mechanism, such as one or more hinges, capable of separating the waveguide 2522 into two parts that can be separated. The mechanism may be used to enable mounting of the waveguide 2522 onto a core 2528 that has no endpoints. Other mechanisms for mounting the waveguide 2522 of FIG. 25C on the core 2528 are contemplated by the subject disclosure. For example, waveguide 2522 may be configured with a slot opening longitudinally spanning the entire waveguide structure. In the slotted design of waveguide 2522 , regions 2522C′ and 2522C of waveguide 2522 may be configured such that inner surface 2523 of waveguide 2522 is closely coupled to the outer surface of core 2528 . The tight coupling between the inner surface 2523 of the waveguide 2522 and the outer surface of the core 2528 prevents sliding or movement of the waveguide 2522 relative to the core 2528 . The tight coupling in regions 2522C' and 2522C may also apply to the hinged design of waveguide 2522.

The waveguide 2522 shown in Figures 25A, 25B, and 25C can be adapted to perform one or more of the embodiments described in other figures of the subject disclosure. Accordingly, it is contemplated that such embodiments may be applied to the waveguide 2522 of Figures 25A, 25B and 25C. Additionally, any adaptations to the core in the subject disclosure can be applied to the waveguide 2522 of Figures 25A, 25B, and 25C.

Although the corresponding process is shown and described as a series of blocks in FIG. 24 for simplicity of illustration, it should be understood and appreciated that claimed subject matter is not limited by the order of the blocks, as some The blocks may occur in a different order and/or concurrently with other blocks than depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methodologies described below.

It should be further noted that the waveguide launch station 2522 of FIGS. 25A-25D and/or the figures (e.g., FIGS. 7-14, 18N-18W, 22A-22B, and other figures) of the subject disclosure Other waveguide launch stations described and illustrated, and any method thereof, may be adapted to generate a waveguide waveguide on a transmission medium having an outer surface composed of, for example, a dielectric material (e.g., an insulator, an oxide, or other material having dielectric properties). A single wave mode or combination of wave modes that reduces propagation loss when propagating through a substance such as a liquid (eg, water produced by moisture, snow, dew, sleet, and/or rain) disposed on the outer surface of a transmission medium.

Figure 25E, Figure 25F, Figure 25G, Figure 25H, Figure 25I, Figure 25J, Figure 25K, Figure 25L, Figure 25M, Figure 25N, Figure 25O, Figure 25P, Figure 25Q, Figure 25R, Figure 25S and Figure 25T are illustrations A block diagram of an exemplary, non-limiting embodiment of a wave pattern (and an electric field profile associated therewith) that may be generated on an outer surface of a transmission medium by one or more of the waveguides of the subject disclosure and adaptations thereof is presented. Turning first to FIG. 25E , an illustration depicting a longitudinal cross-section of the transmission medium 2542 is provided. The transmission medium 2542 may include a conductor 2543, a dielectric material 2544 (e.g., insulator, oxide, etc.) disposed on the conductor 2543, and a substance/water film 2545 (or water, liquid, or other other accumulations of matter). Transmission medium 2542 may be exposed to a gaseous substance such as the atmosphere or air 2546 (or may be located in a vacuum). The respective thicknesses of conductor 2543, dielectric material 2544, and water film 2545 are not drawn to scale and are therefore intended to be illustrative only. Although not shown in FIG. 25E , conductor 2543 may be a cylindrical conductor surrounded by dielectric material 2544 and air 2546 (eg, a single conductor, multiple braided conductors, etc.). To simplify the description of the subject disclosure, only a portion of conductor 2543 proximate the upper (first) surface is shown. Furthermore, symmetrical portions of dielectric material 2544, water film 2545 and air 2546 that would be below (or on the opposite/bottom side of) conductor 2543 are not shown in the longitudinal cross-section of FIG. 25E.

In some embodiments, gravity can cause the water film 2545 to concentrate primarily on a restricted portion of the outer surface of the transmission medium 2542 (eg, on the bottom side of the transmission medium 2542). Thus, the outer surface of the dielectric material need not be completely surrounded by the water film 2545 in this illustration. It should be further noted that the water film 2545 may be water droplets or beads rather than a continuous water film. Although FIG. 25E illustrates insulated conductors (i.e., conductor 2543 surrounded by dielectric material 2544), other configurations of transmission medium 2542 are possible and applicable to the subject disclosure, such as, for example, comprised of bare wire or other uninsulated conductors. The transmission medium 2542 is made of only dielectric materials with various structural shapes (eg, cylindrical structure, rectangular structure, square structure).

25E further depicts the electric field of a fundamental transverse magnetic wave mode in the form of a TM00 wave mode (sometimes referred to as a Goubau wave mode) produced by one of the waveguide launching stations described in the subject disclosure or an adaptation thereof. The emission is onto the outer surface of the transmission medium 2542 and travels in a longitudinal direction along the transmission medium 2542 corresponding to the direction of wave propagation as shown. An electromagnetic wave propagating along a transmission medium via a transverse magnetic (TM) mode has an electric field with two radial rho field components extending radially outward from the transmission medium and perpendicular to the longitudinal direction, and according to propagation parallel to the longitudinal direction It has a longitudinal z field component that varies with time and distance, but does not have an azimuthal phi field component that is perpendicular to the longitudinal and radial directions.

The TM00 Goubau wave mode produces an electric field in region 2550 with a predominant radial rho field component extending through the dielectric at high field strength away from the conductor. The TM00 Goubau wave mode also produces an electric field in region 2550" with a predominant radial rho field component extending through the dielectric into the conductor at high field strength. In addition, region 2550' between regions 2550 and 2550" In , an electric field with a smaller magnitude and with a dominant longitudinal z-field component is generated. The presence of these electric fields inside the dielectric causes some attenuation, but losses in these regions are insignificant compared to the effects of thin water films as will be discussed below.

An expanded view 2548 of a smaller region of the transmission medium 2542 (as depicted by the dashed oval) is shown at the lower right of Figure 25E. Expanded view 2548 depicts a higher resolution of the electric field present in a smaller region of transmission medium 2542 . The expanded view shows the electric field in the dielectric material 2544 , water film 2545 and air 2546 . Most of the electric field depicted in region 2547 of expanded view 2548 has a significant longitudinal component, especially in the region near the outer surface of the dielectric material 2544 in the region of water film 2545 . When an electromagnetic wave exhibiting a TM00 (Goubau) wave mode propagates longitudinally (from left to right or from right to left), the region of the stronger longitudinal component of the electric field shown in region 2547 enables the electric field to traverse more of the water film 2545. Mostly, resulting in substantial propagation loss, for example, the attenuation of the propagation loss may be of the order of 200 dB/M for frequencies in the range of 24 GHz to 40 GHz.

Figure 25F depicts a cross-sectional longitudinal view of a simulated electromagnetic wave with a TM00 (Goubau) wave mode, and the effect when such waves propagate on dry and wet transmission media 2542 implemented as 1 meter (length) insulated conductors. For illustration purposes only, the simulations assume a non-destructive insulator to focus the analysis on the extent of attenuation caused by a 0.1 mm water film. As shown in the illustration, when an electromagnetic wave having a TM00 (Goubau) wave mode propagates on a dry transmission medium 2452, the wave experiences minimal propagation loss. In contrast, when the same electromagnetic wave having the TM00 (Goubau) wave mode propagates in the moist transmission medium 2542, for example for frequencies in the range of 24 GHz to 40 GHz, the electromagnetic wave is subjected to an insulated conductor of greater than 200 dB on a length of 1 meter. Significant propagation loss attenuation.

FIG. 25G illustrates a simulation depicting the amplitude and frequency properties of electromagnetic waves propagating on a dry insulated conductor 2542 and a wet insulated conductor 2542 with a TM00 Goubau wave mode. For illustration purposes only, the simulations assume a non-destructive insulator to focus the analysis on the extent of attenuation caused by a 0.1 mm water film. The graph shows that, when the transmission medium 2542 is wet, electromagnetic waves with a TM00 Goubau wave mode experience an attenuation of approximately 200 dB/M for the frequency range 24 GHz to 40 GHz. In comparison, the plot of dry insulated conductor 2542 suffers little attenuation over the same frequency range.

25H and 25I illustrate the electric field plots of electromagnetic waves with TM00 Goubau wave mode operating at 3.5 GHz and 10 GHz, respectively. Although the vertical axis represents field strength rather than distance, dashed lines have been superimposed on the graphs of FIGS. 25H and 25I (and the graphs of FIGS. to delineate the corresponding parts of the conductor, insulator and water film. Although the field strengths in FIGS. 25H and 25I (and the graphs of FIGS. 25M to 25S ) were calculated based on the absence of water, the graphs shown in FIG. The lower frequency TM00 Goubau wave modes have lower propagation losses in the presence of water in the locations shown on the outer surface of .

In order to understand the graphs of Figures 25H and 25I, it is important to understand the difference between the radial rho field and the longitudinal z field. When looking at a longitudinal cross-section of the transmission medium 2542 as shown in FIG. 25E , the rho field is indicated from the conductor 2543 outward through the dielectric material 2544, the possible presence of a water film 2545, and the air 2546, or inward toward the conductor ( An electric field extending radially perpendicular to the longitudinal axis). In contrast, the z-field is the electric field aligned with the dielectric material 2544 , the water film 2545 , or the air 2546 in a manner parallel to the longitudinal axis of the transmission medium 2542 . When the electromagnetic wave propagates longitudinally (from left to right or right to left) along the outer surface of the transmission medium 2542, the propagating electromagnetic wave having only an electric field component radially or perpendicular to the water film 2545 does not suffer significant field strength loss. In contrast, when an electromagnetic wave propagates longitudinally (from left to right or from right to left) along the outer surface of the transmission medium 2542, there is a parallel (or longitudinal) electric field component (i.e., a z field aligned with the water film 2545 ), propagating electromagnetic waves with field strengths significantly greater than zero will suffer significant field strength loss (ie, propagation loss).

In the case of the TM00 Goubau wave mode at 3.5 GHz as shown in the graph of FIG. 25H , starting from the outer surface of the dielectric material 2544 and passing through where the water film 2545 may exist, the z field component of the electric field has a relative Smaller field strengths in terms of the rho field (radial) component, as shown in Figure 25H. In particular, graph 25H indicates the magnitude of the field strength of the rho field component and the z field component at the point in time when the field strength is at its peak value as a function of radial distance from the center of the transmission medium. Although the field strengths were calculated based on the absence of water, the graph shown in Figure 25G still helps explain why the lower frequency TM00 Goubau The wave mode has lower propagation loss. Indeed, according to an embodiment, regions where the electric field has a large radial component perpendicular to the direction of propagation (e.g. radial rho field) and conversely has a relatively small longitudinal component (e.g. z field), it can have relatively low propagation loss. Therefore, when the water film 2545 is disposed on the outer surface of the dielectric material 2544 (due to rain, snow, dew, sleet, and/or excess moisture), electromagnetic waves with a TM00 Goubau wave mode of 3.5 GHz will not experience a significant amount of attenuation. However, this is not true for all frequencies, especially as the frequencies approach the mmWave range.

For example, Figure 251 depicts a graph of the TM00 wave pattern at 10 GHz. In this graph, the field strength of the z field component in the water film region is relatively large when compared to the rho field (radial) component. Therefore, the propagation loss is very high. Figure 25J shows that when there is a water film with a thickness of 0.1 mm on the outer surface of the insulated conductor, the TM00 wave mode at 4 GHz suffers an attenuation of 0.62 dB/M, which is significantly lower than the TM00 wave at 10 GHz, which suffers an attenuation of 45 dB/M model. Therefore, the TM00 wave mode operating at high frequencies up to millimeter-wave frequencies can suffer substantial propagation loss in the presence of a water film on the outer surface of the transmission medium.

Turning now to FIG. 25K , a diagram depicting electromagnetic waves propagating on an outer surface of dielectric material 2544 having a TM01 wave mode (eg, a non-fundamental mode) is provided. In expanded view 2548, region 2547 demonstrates that the electric field of the electromagnetic wave with TM01 wave mode has a significant radial rho field component, and an insignificant longitudinal z in the region near the outer surface of the dielectric material 2544 in the region of the water film 2545 field component. The TM01 wave mode has a cutoff frequency greater than zero Hertz. When an electromagnetic wave having a TM01 wave mode is configured by a waveguide launch station of the subject disclosure (its adaptation or other launch station) to operate in a frequency range around its cutoff frequency, a small fraction of the power is carried by the dielectric material 2544 and Most of the power is concentrated in the air 2546.

The TM01 wave mode produces an electric field in region 2551 with a predominant radial rho field component extending away from the conductor, which is reversed in dielectric 2544 and directed inwardly from the air at the surface of the dielectric 2544. The TM01 wave mode also produces in region 2551" an electric field with a predominant radial rho field component extending into the conductor that is inverted in dielectric 2544 and directed outward from dielectric 2544 at the surface of the dielectric Air. Furthermore, in region 2551' between regions 2551 and 2551", an electric field is generated within dielectric layer 2544 with a predominant longitudinal z-field component. As in the case of the TM00 mode, the presence of these electric fields within the dielectric 2544 will produce some attenuation, but the losses in these regions may not be sufficient to prevent the propagation of the TM01 wave over considerable distances.

Additionally, the electric field of the TM01 wave mode in region 2547 of water film 2545 is predominantly radial with a relatively insignificant longitudinal component. Therefore, when an electromagnetic wave having such a field structure propagates longitudinally (from left to right or from right to left) along the outer surface of the transmission medium 2542, the propagating wave will not suffer a large propagation loss.

Figure 25L depicts a cross-sectional longitudinal view of an electromagnetic wave having a TM01 wave mode and the effect when such a wave propagates at millimeter wave frequencies or slightly lower on dry and moist transmission media 2542. As shown in the illustration, when an electromagnetic wave having a TM01 wave mode propagates on dry transmission medium 2452, the wave experiences minimal propagation loss. Electromagnetic waves having the TM01 wave mode experience only modest additional attenuation when propagating in the moist transmission medium 2542 compared to electromagnetic waves having the TM00 Goubau wave mode of similar frequency. For example, electromagnetic waves with a TM01 wave mode in the millimeter frequency range are therefore less susceptible to increased propagation loss than electromagnetic waves with a TM00 Goubau wave mode in this same frequency range due to the presence of the water film 2545.

25M provides an illustration of an electric field plot of the radial rho field component and the longitudinal z field component of the electric field of the TM01 wave mode with an operating frequency of 30.437 GHz, which is 50 MHz higher than the cutoff frequency of the wave mode. Based on a 4mm radius of the conductor 2543 and a 4mm thickness of the dielectric material 2544, the cutoff frequency is at 30.387GHz. When the dimensions of the conductor 2543 and dielectric material 2544 are different than this illustration, the TM01 wave mode may have a higher or lower cutoff frequency. In particular, the graph indicates the magnitude of the field strength at the point in time when the magnitude of the field strength of the rho field component and the z field component is at its peak value, as a function of the radial distance away from the center of the transmission medium . Although the field strength was calculated based on the absence of water, the graph shown in Figure 25M still helps to explain why the TM01 wave mode has a lower propagation loss. As noted earlier, an electric field substantially perpendicular to the water film 2545 suffers no significant loss of field strength, whereas an electric field parallel/longitudinal to the outer surface of the dielectric material 2544 in the region of the water film 2545 will have this field structure The electromagnetic wave undergoes significant field strength loss when propagating along the transmission medium 2542.

In the case of the TM01 wave mode, starting from the outer surface of the dielectric material 2544 and passing through the water film 2545, the longitudinal z-field component of the electric field can have a very small field strength relative to the magnitude of the radial field, as shown in Figure 25M shown in . Therefore, when the water film 2545 is disposed on the outer surface of the dielectric material 2544 (due to rain, dew, snow, sleet, and/or excess moisture), electromagnetic waves having a TM01 wave mode of 30.437 GHz will experience a greater than 6 GHz ( For example, there is much less attenuation of the TM00 Goubau wave mode at frequencies of 10 GHz—see FIG. 25J ).

Figure 25N illustrates a graph depicting the amplitude and frequency properties of electromagnetic waves propagating on a dry transmission medium 2542 and a moist transmission medium 2542 having a TM01 wave mode. The graph shows that when the transmission medium 2542 is wet, electromagnetic waves with a TM01 wave mode undergo moderate attenuation when the TM01 wave mode operates in a frequency range around its cutoff frequency (eg, 28 GHz to 31 GHz). In comparison, the TM00 Goubau wave mode suffers a significant attenuation of 200 dB/M over this same frequency range as shown in the graph of Fig. 25G. The graph of Figure 25N thus confirms the results of the dry versus wet simulations shown in Figure 25L.

Figures 25O, 25P, 25Q, 25R and 25S depict other wave modes that may exhibit properties similar to those shown for the TM01 wave mode. For example, FIG. 25O provides an illustration of an electric field plot for the radial rho field component and the longitudinal z field component of the electric field of a TM02 wave mode with an operating frequency of 61.121 GHz, which is higher than the cutoff frequency of the wave mode. 50MHz. As noted above, the cutoff frequency may be higher or lower when the conductor 2543 and dielectric material 2544 are sized differently than this illustration. In particular, the graph indicates the magnitude of the field strength at the point in time when the magnitude of the field strength of the rho field component and the z field component is at its peak value, as a function of the radial distance away from the center of the transmission medium . Although the field strengths were calculated based on the absence of water, starting from the outer surface of the dielectric material 2544 and passing through the location that would be occupied by the water film 2545, the z-field component of the electric field may have a magnitude relative to the radial rho field. For very small field strengths, as shown in Figure 25O. Accordingly, electromagnetic waves exhibiting a TM02 wave mode will experience much less attenuation due to the accumulation of water on the outer surface of the dielectric layer than wave modes with a more pronounced longitudinal z-field component in locations corresponding to the water film.

Figure 25P provides an illustration of an electric field plot of the radial rho field component, the longitudinal z field component and the azimuthal phi field component of the electric field of a mixed wave mode; specifically the EH11 wave with an operating frequency of 31.153 GHz mode, the operating frequency is 50 MHz higher than the cutoff frequency of the wave mode. As previously mentioned, depending on the dimensions of the conductor 2543 and dielectric material 2544, the cutoff frequency in the illustration of FIG. 25P can be higher or lower.

Non-TM wave modes, such as hybrid EH wave modes, may have an azimuthal field component that is perpendicular to the radial rho field component and the longitudinal z field component and that surrounds the transmission medium tangentially in a clockwise and/or counterclockwise direction The circumference of 2542. Like the z-field component, the phi field (azimuth) component at the outer surface of the dielectric 2544 can lead to significant propagation losses in the presence of a thin water film 2545 . The graph of FIG. 25P indicates the magnitude of the field strength at the point in time when the magnitude of the field strength of the rho field component, phi field component, and z field component is at its peak value, as a radial direction away from the center of the transmission medium 2542. function of distance. Although the field strengths were calculated based on the absence of water, starting from the outer surface of the dielectric material 2544 and passing through the location that would be occupied by the water film 2545, the z and phi field components of the electric field each have a relative Very small field strengths in terms of magnitude. Therefore, an electromagnetic wave with an EH11 wave mode will experience much less due to the accumulation of water on the outer surface of the dielectric layer than a wave mode with a more pronounced longitudinal z-field component and phi field component in the position corresponding to the water film attenuation.

Figure 25Q provides an illustration of an electric field plot of the radial rho field component, the longitudinal z field component and the azimuthal phi field component of the electric field of a higher order mixed wave mode; An EH12 wave mode of operating frequency that is 50 MHz higher than the cutoff frequency of the wave mode. As previously stated, depending on the dimensions of the conductor 2543 and dielectric material 2544, the cutoff frequency may be higher or lower. Specifically, the graph indicates the magnitude of the field strength at the time point when the magnitude of the field strength of the rho field component, phi field component, and z field component is at its peak value, as a path away from the center of the transmission medium function of distance. Although the field strengths were calculated based on the absence of water, starting from the outer surface of the dielectric material 2544 and passing through the location that would be occupied by the water film 2545, the z and phi field components of the electric field each have a relative Very small field strengths in terms of magnitude. Therefore, an electromagnetic wave exhibiting the EH12 wave mode will experience much less due to the accumulation of water on the outer surface of the dielectric layer than a wave mode with more pronounced longitudinal z and phi field components in the location corresponding to the water film. attenuation.

Figure 25R provides an illustration of an electric field plot of the radial rho field component, the longitudinal z field component, and the azimuthal phi field component of the electric field of a mixed wave mode; specifically HE22 waves with an operating frequency of 36.281 GHz mode, the operating frequency is 50 MHz higher than the cutoff frequency of the wave mode. As previously stated, depending on the dimensions of the conductor 2543 and dielectric material 2544, the cutoff frequency may be higher or lower. Specifically, the graph indicates the magnitude of the field strength at the time point when the magnitude of the field strength of the rho field component, phi field component, and z field component is at its peak value, as a path away from the center of the transmission medium function of distance. Although the field strengths were calculated based on the absence of water, starting from the outer surface of the dielectric material 2544 and passing through the location that would be occupied by the water film 2545, the z and phi field components of the electric field each have a relative Smaller field strengths in terms of magnitude. Thus, an electromagnetic wave exhibiting the EH22 wave mode will experience much less due to the accumulation of water on the outer surface of the dielectric layer than a wave mode with more pronounced longitudinal z-field and phi field components in the location corresponding to the water film. attenuation.

Figure 25S provides an illustration of the electric field plots of the radial rho field component, the longitudinal z field component and the azimuthal phi field component of the electric field of the higher order mixed wave mode; HE23 wave mode at an operating frequency that is 50 MHz higher than the cutoff frequency of the wave mode. As previously stated, depending on the dimensions of the conductor 2543 and dielectric material 2544, the cutoff frequency may be higher or lower. Specifically, the graph indicates the magnitude of the field strength at the time point when the magnitude of the field strength of the rho field component, phi field component, and z field component is at its peak value, as a path away from the center of the transmission medium function of distance. Although the field strengths were calculated based on the absence of water, starting from the outer surface of the dielectric material 2544 and passing through the location that would be occupied by the water film 2545, the z and phi field components of the electric field each have a relative Smaller field strengths in terms of magnitude. Therefore, an electromagnetic wave exhibiting a HE23 wave mode will experience much less due to the accumulation of water on the outer surface of the dielectric layer than a wave mode with a more pronounced longitudinal z-field component and phi field component in the location corresponding to the water film. attenuation.

Based on observations of the electric field plots of Figure 25M and Figure 25O, it can be considered that an electromagnetic wave with a TM0m wave mode (where m > 0) will experience a more significant longitudinal z-field component and and/or less propagation loss in the wave mode of the phi field component. Similarly, based on observations of the electric field plots of Figures 25P to 25Q, it can be argued that electromagnetic waves with the EH1m wave mode (where m > 0) will experience a more pronounced longitudinal z Less propagation loss for wave modes of field components and/or phi field components. Additionally, based on observations of the electric field plots of Figures 25R to 25S, it is believed that electromagnetic waves with HE2m wave modes (where m > 1) will experience a more significant longitudinal z-field than in locations corresponding to water films component and/or phi field component wave modes with less propagation loss.

It should be further noted that the waveguide launch station 2522 of FIGS. 25A-25D and/or the figures (e.g., FIGS. 7-14, 18N-18W, 22A-22B, and other figures) of the subject disclosure Other waveguide launch stations described and illustrated may be adapted to generate or induce a TM0m-wave mode or EH1m-wave mode (where m > 0), HE2m-wave mode (where m > 1), or exhibit z-field components (and azimuth field component, if present), of any other type of wave mode of lower field strength. Since certain wave modes have an electric field structure that is less susceptible to propagation loss near the outer surface of the transmission medium, the electromagnetic wave launching pads of the subject disclosure can be adapted to generate Electromagnetic wave(s) having the above wave mode properties in order to reduce propagation loss when propagating through substances such as liquids (eg, water produced by moisture and/or rain) disposed on the outer surface of the transmission medium. It should be further noted that, in some embodiments, the transmission medium used to propagate one or more of the above wave modes may consist solely of dielectric materials.

Referring back to the TM01 wave pattern of FIG. 25K, it should also be noted that region 2549 in expanded view 2548 shows electric field vectors exhibiting eddy current behavior (eg, a circular or swirly pattern). While it appears that some of the electric field vectors in region 2549 have longitudinal field components located within water film 2545, these vectors have Very low field strength and much less in number. However, these few electric field vectors with non-zero longitudinal components in region 2549 may be contributing factors to the modest attenuation described earlier with respect to moist transmission medium 2542 of FIG. 25L. The detrimental effect of the electric field vectors in the small eddy current region 2549 of FIG. 25K is that of a considerably larger number of electric field vectors with a significant longitudinal component in the region 2547 of the TM00 Gaubau wave mode of FIG. ) have much less adverse effects. As noted earlier, the electric field vector in the region 2547 of the TM00 Gaubau wave mode results in a much higher Propagation loss (up to 200dB/M attenuation), for TM01 wave mode, this is not the case.

It should also be noted that the electric field depictions in Figure 25E and Figure 25K are not static in time and space. That is, as the electromagnetic wave propagates spatially longitudinally along the transmission medium, the electric field associated with the electromagnetic wave changes when viewed at a static location on the transmission medium over time. Thus, the electric field graphs shown in Figures 25H, 25I, 25M, and 25O-25S are non-static and can expand and contract, as well as reverse in polarity. Even if the electric field profile is not static, the mean field of the z-field component (and the azimuthal field component, when present) of the TM0m-wave mode and the EH1m-wave mode (where m > 0) and the HE2m-wave mode (where m > 1) The field strength is also much lower than that exhibited by the z-field component of the TM00 Goubau wave mode above 6 GHz. Thus, the TM0m-wave mode and the EH1m-wave mode (where m>0) and the HE2m-wave mode (where m>1) in the presence of the water film 2545 experience higher frequency than the TM00 Goubau-wave mode in the frequency range above 6 GHz much lower propagation loss.

It should be further pointed out that the electric field of the TM00 Goubau wave mode is quite different from the TM0m wave mode and EH1m wave mode (where m>0) and HE2m wave mode (where m>1). Take for example the electric fields of the TM00 Goubau wave mode and the TM01 wave mode depicted in the orthogonal cross-sectional view of the transmission medium 2542 shown in FIG. 25T. The TM00 Goubau wave mode depicts a radial electric field extending away from the conductor at high field strength through the dielectric. This behavior is depicted in region 2550 of Figure 25E in the temporal and spatial instance of transmission medium 2542. In contrast, the TM01 wave pattern depicts an electric field extending away from the conductor, with a large decrease in field strength at the midpoint of the dielectric, and a reversal of polarity and an increase in field strength towards the outer surface of the dielectric. This behavior is depicted in region 2551 of FIG. 25K in the temporal and spatial instance of transmission medium 2542 .

If the cross-sectional slice shown in FIG. 25T remains constant over time, then in the TM00 Goubau wave mode, the electric field in region 2550' (of FIG. 25E ) will arrive in time at the cross-sectional slice where the field strength decreases, and in the region The electric field in 2550" reaches the cross-sectional slice with an abrupt polarity reversal. In contrast, in the TM01 wave mode, the electric field in region 2551' (of FIG. 25K) will arrive in time to become longitudinal (i.e., from pointing outwards) so that the electric field shown for the TM01 wave mode in FIG. Polarity returns where the polarity starts to reverse.

It will be appreciated that the electromagnetic wave patterns described in FIGS. 25E-25T and in other parts of the subject disclosure may be described in whole or in part in the subject disclosure (eg, FIGS. 18A-18L ). Multiple wave modes are emitted, either individually or in combination, on the outer surface of the transmission medium, or embedded within any of the transmission medium. It should be further noted that these electromagnetic wave patterns can be converted to wireless signals by any of the antennas described in the subject disclosure (e.g., FIGS. 18M , 19A-19F , 20A-20F ), or received The wireless signal is converted back to one or more electromagnetic waves that propagate along one of the above-mentioned transmission media. The methods and systems described in the subject disclosure may also be applied to these electromagnetic waves for the purpose of transmitting, receiving or processing, or adapting or modifying, these electromagnetic wave patterns. It should be further noted that any of the waveguide launch stations (or adaptations thereof) may be configured to induce or generate one or more target field structures or target wave modes with spatial alignment exhibiting electric fields on the transmission medium. electromagnetic waves for the purpose of reducing propagation loss and/or signal interference. The waveguide device of Figure 25U provides a non-limiting illustration of the adaptation of a waveguide launch station of the subject disclosure.

Turning now to FIG. 25U , which illustrates a simplified diagram of an example non-limiting embodiment of a waveguide device 2522 in accordance with various aspects described herein. The waveguide device 2522 is similar to the waveguide device 2522 shown in Figure 25C, with few adaptations. In the illustration of FIG. 25U, a waveguide device 2522 is coupled to a transmission medium 2542 comprising a conductor 2543 and an insulating layer 2543 which together form an insulated conductor, such as the insulated conductors shown in the drawings of FIGS. 25E and 25K. conductor. Although not shown, the waveguide device 2522 may be composed of two halves that may be connected together at one longitudinal end using one or more mechanical hinges to enable movement between opposite sides of the one or more hinges. The longitudinal edges are open at the ends to allow placement of the waveguide device 2522 on the transmission medium 2542 . Once placed, one or more latches at the longitudinal edge opposite the one or more hinges may be used to secure the waveguide device 2522 to the transmission medium 2542 . Other embodiments for coupling waveguide device 2522 to transmission medium 2542 may be used with, and are thus contemplated by, the subject disclosure.

The chamber 2525 of the waveguide device 2522 of Figure 25U includes a dielectric material 2544'. The dielectric material 2544' in the chamber 2525 may have a dielectric constant similar to the dielectric constant of the dielectric layer 2544 of the insulated conductor. Additionally, a disc 2525' with a central hole 2525" can be used to divide the chamber 2525 into two halves for the transmission or reception of electromagnetic waves. The disc 2525' can be configured by not allowing electromagnetic waves to travel between the halves of the chamber 2525 material (e.g., carbon, metal, or other reflective material). As shown in FIG. near the outer surface of the dielectric layer 2543. Figure 25U shows an expanded view 2524A' of a MMIC 2524' including an antenna 2524B' (such as a monopole, dipole, or other antenna) that may be configured to communicate with a transmission medium 2542 The outer surface of the dielectric layer 2543 is aligned longitudinally. The antenna 2524B' may be configured to radiate a signal having a longitudinal electric field directed eastward or westward, as will be discussed later. It will be appreciated that the radiation may have a longitudinal electric field Other antenna structures for signals of electric fields may be used in place of dipole antenna 2524B' of FIG. 25U.

It will be appreciated that although two MMICs 2524' are shown in each half of the chamber 2525 of the waveguide device 2522, many more MMICs may be used. For example, FIG. 18W shows a transverse cross-sectional view of a cable (such as transmission medium 2542) surrounded by a waveguide device with 8 MMICs located in the following locations: north, south, east, west, northeast, northwest, southeast, and southwest. For purposes of illustration, the two MMICs 2524' shown in Figure 25U may be considered to be MMICs 2524' in the northern and southern locations shown in Figure 18W. The waveguide device 2522 of Figure 25U may be further configured with MMICs 2524' in the western and eastern positions shown in Figure 18W. In addition, the waveguide device 2522 of Figure 25U may be further configured with MMICs in the northwest, northeast, southwest, and southeast locations as shown in Figure 18W. Accordingly, waveguide device 2522 may be configured with more than the 2 MMICs shown in Figure 25U.

With this in mind, attention now turns to Figures 25V, 25W, 25X, which illustrate diagrams of exemplary non-limiting embodiments of wave patterns and electric field profiles in accordance with various aspects described herein. Figure 25V illustrates the electric field of the TM01 wave mode. These electric fields are illustrated in a transverse cross-sectional view (top) and a longitudinal cross-sectional view (below) of a coaxial cable with a center conductor of an outer conductive shield separated by an insulator. Figure 25W illustrates the electric field of the TM11 wave mode. These electric fields are also illustrated in transverse and longitudinal cross-sectional views of a coaxial cable having a center conductor of an outer conductive shield separated by an insulator. Figure 25X further illustrates the electric field of the TM21 wave mode. These electric fields are illustrated in transverse and longitudinal cross-sectional views of a coaxial cable having a center conductor of an outer conductive shield separated by an insulator.

As shown in the transverse cross-sectional views, the TM01 wave modes have circularly symmetric electric fields (i.e., electric fields with the same orientation and strength at different azimuths), while the TM11 wave modes shown in Fig. 25W to Fig. 25X, respectively The transverse cross-sectional views of the modes and TM21 wave modes have non-circular symmetric electric fields (ie, electric fields with different orientations and strengths at different azimuths). Although the transverse cross-sectional views of the TM11 wave mode and the TM21 wave mode have non-circular symmetric electric fields, the electric fields in the longitudinal cross-sectional views of the TM01 wave mode, TM11 wave mode, and TM21 wave mode are basically similar, the difference being that the TM11 wave mode The electric field structure has longitudinal electric fields pointing in opposite longitudinal directions above and below the conductor, while the longitudinal electric fields above and below the conductor of TM01 wave mode and TM21 wave mode point to the same longitudinal direction.

The longitudinal cross-sectional views of the coaxial cables of Figures 25V, 25W and 25X can be considered to have a similar structural arrangement as the longitudinal cross-section of the waveguide device 2522 in region 2506' shown in Figure 25U. Specifically, in FIGS. 25V, 25W, and 25X, the coaxial cable has a center conductor and shield separated by an insulator, while region 2506' of waveguide device 2522 has center conductor 2543 covered by dielectric material 2544' of chamber 2525. And the dielectric layer 2544 shielded by the reflective inner surface 2523 of the waveguide device 2522 . The coaxial configuration in region 2506' of waveguide device 2522 continues in tapered region 2506" of waveguide device 2522. Similarly, the coaxial configuration continues in regions 2508 and 2510 of waveguide device 2522, with the difference that, in addition to Dielectric material 2544' is absent in those regions of transmission medium 2542 outside dielectric layer 2544. At outer region 2512, transmission medium 2542 is exposed to the environment (eg, air) and thus the coaxial configuration no longer exists.

As noted earlier, in the transverse cross-sectional view of the coaxial cable shown in Figure 25V, the electric field structure of the TM01 wave mode is circularly symmetric. For purposes of illustration, it will be assumed that the waveguide device 2522 of Figure 25U has 4 MMICs located in the North, South, West and East locations as depicted in Figure 18W. In this configuration and with an understanding of the longitudinal and transverse electric field structures of the TM01 wave mode shown in FIG. 25V, the four MMICs 2524' of the waveguide device 2522 in FIG. Transmit TM01 wave patterns from a common source. This can be accomplished by configuring the North, South, East and West MMICs 2524' to transmit wireless signals with the same phase (polarity). The wireless signals generated by the four MMICs 2524' are combined by superimposing their respective electric fields in the dielectric material 2544' of the chamber 2525 and the dielectric layer 2544 (since the two dielectric materials have similar dielectric constants) so that A TM01 electromagnetic wave 2502' confined to these dielectric materials is formed having the electric field structure shown in the longitudinal and transverse views of FIG. 25V.

Electromagnetic wave 2502 ′ having TM01 wave mode in turn propagates towards tapered structure 2522B of waveguide device 2522 and thereby becomes electromagnetic wave 2504 ′ embedded in dielectric layer 2544 of transmission medium 2542 ′ in region 2508 . In the tapered horn section 2522D, the electromagnetic wave 2504' having the TM01 wave mode spreads in the region 2510 and eventually exits the waveguide device 2522 without changing the TM01 wave mode.

In another embodiment, waveguide device 2522 may be configured to emit a TM11 wave mode with vertical polarity in region 2506'. This can be accomplished by configuring the MMIC 2524' in the northern location to radiate a first wireless signal from a signal source that is in phase (polarity) different from the second wireless signal radiated by the southern MMIC 2524' from the same source. The phase (polarity) of the signal is reversed. These wireless signals combine by superimposing their respective electric fields to form electromagnetic waves with a dielectric having a TM11 wave mode (vertical polarization), which is confined to the dielectric material 2544' and 2544, with longitudinal cross-sectional views in Figure 25W and The electric field structure shown in the lateral cross-sectional view. Similarly, waveguide device 2522 may be configured to emit a TM11 wave mode with horizontal polarity in region 2506'. This can be accomplished by configuring the MMIC 2524' in the eastern location to radiate a first wireless signal that has an opposite phase (polarity) to that of the second wireless signal radiated by the western MMIC 2524'. ).

These wireless signals combine by superimposing their respective electric fields to form a dielectric electromagnetic wave 2502' having a TM11 wave mode (horizontal polarization), which is confined to the dielectric material 2544' and 2544, having a longitudinal cross-sectional view in FIG. 25W and the electric field structure shown in the transverse cross-sectional view (but with horizontal polarization). Since the TM11 wave modes with horizontal and vertical polarization are orthogonal (i.e., at every point in space and time the dot product of the corresponding electric field vectors between any pair of these wave modes yields a sum of zero) , so the waveguide device 2522 can be configured to transmit these wave modes simultaneously without interference, thereby achieving mode division multiplexing. It should be further noted that the TM01 wave mode is also orthogonal to the TM11 wave mode and the TM21 wave mode.

Although the electromagnetic waves 2502' and 2504' having the TM11 wave mode propagate in the confinement inner regions 2506', 2506", 2508, and 2510 of the inner surface 2523 of the waveguide device 2522, the TM11 wave mode remains unchanged. However, when having the TM11 wave mode When the electromagnetic wave 2504' of the mode exits the waveguide device 2522 in the region 2512, the inner wall 2523 is no longer present, and the TM11 wave mode becomes a hybrid wave mode, specifically, the EH11 wave mode (vertically polarized, horizontally polarized, or both, if If two kinds of electromagnetic waves are emitted in the area 2506').

In still other embodiments, the waveguide device 2522 may also be configured to transmit the TM21 wave mode in the region 2506'. This can be accomplished by configuring the MMIC 2524' in the northern location to radiate a first wireless signal from a signal source that has the same phase (polarity) as the second wireless signal radiated by the southern MMIC 2524' from the same source. ) phase (polarity). Meanwhile, the MMIC 2524' in the west location is configured to radiate a third wireless signal from the same source as the fourth wireless signal radiated by the MMIC 2524' in the east location from the same source. The signal is in phase. However, the north and south MMICs 2524' generate the first and second wireless signals having polarities opposite to those of the third and fourth wireless signals generated by the west and east MMICs 2524'. The fourth wireless signals with alternating polarities combine by superimposing their respective electric fields to form an electromagnetic wave having a TM21 wave mode confined to the dielectric material 2544' and 2544, having the longitudinal cross-sectional view and the transverse direction in FIG. 25X The electric field structure shown in the cross-sectional view. When the electromagnetic wave 2504' exits the waveguide device 2522, it may not be transformed into a mixed wave mode, such as, for example, a HE21 wave mode, an EH21 wave mode, or a mixed wave mode with a different radial mode (e.g., HE2m or EH2m, where m>1).

Figures 25U-25X illustrate several embodiments for transmitting TM01, EH11 and other mixed wave modes utilizing the waveguide device 2522 of Figure 25U. With an understanding of the electric field structure of other wave modes (e.g., TM12, TM22, etc.) Other wave modes (e.g., EH12, HE22, etc.) that have lower intensity z-field components and phi-field components in the 2542, which help mitigate the effects of electromagnetic waves such as water, water droplets, or Propagation loss caused by substances such as other substances that attenuate the electric field.

Figure 25Y illustrates a flowchart of an example non-limiting embodiment of a method 2560 for sending and receiving electromagnetic waves. Method 2560 may be applied to waveguide 2522 of FIGS. 25A-25D and/or as described in the figures of the subject disclosure (e.g., FIGS. 7-14, 18N-18W, 22A-22B, and others). and other waveguide systems or launch pads as shown for the purpose of transmitting or receiving substantially orthogonal wave modes as shown in Figure 25Z. Figure 25Z depicts three cross-sectional views of an insulated conductor in which the TM00 fundamental mode, the HE11 wave mode with horizontal polarization, and the HE11 wave mode with vertical polarization propagate, respectively. The electric field structure shown in Figure 25Z may vary over time and is thus an illustrative representation of some instance or snapshot in time. The wave modes shown in Figure 25Z are orthogonal to each other. That is, the dot product of the corresponding electric field vectors between any pair of these wave modes at every point in space and time yields a sum of zero. This property enables the TM00 wave mode, the HE11 wave mode with horizontal polarization, and the HE11 wave mode with vertical polarization to propagate simultaneously in the same frequency band along the surface of the same transmission medium without signal interference.

With this in mind, method 2560 can begin at step 2562, where the waveguide system of the subject disclosure can be adapted for transmitting from a source (e.g., a base station, by a mobile device, or a stationary device) to the subject disclosure wireless signals to the antenna of the waveguide system described in the content, or receive communication signals through another communication source). The communication signal may be, for example, a communication signal modulated according to a particular signaling protocol (LTE, 5G, DOCSIS, DSL, etc.) analog signals, other signals, or a combination thereof. At step 2564, the waveguide system may be adapted to transmit the communication signal over the transmission medium in accordance with the communication signal by upconverting (or, in some cases, downconverting) such communication signal to one or more operating frequencies of a plurality of electromagnetic waves. The plurality of electromagnetic waves are generated or emitted. The transmission medium may be an insulated conductor as shown in Figure 25AA, or an uninsulated conductor subjected to oxidation (or other chemical reaction based on environmental exposure) from environmental exposure as shown in Figures 25AB and 25AC. In other embodiments, the transmission medium may be a dielectric material, such as a dielectric core as depicted in Figure 18A.

To avoid interference, the waveguide system may be adapted to simultaneously transmit the first electromagnetic wave using the TM00 wave mode, the second electromagnetic wave using the HE11 wave mode with horizontal polarization, and the HE11 wave mode with vertical polarization at step 2564 Emitting a third electromagnetic wave - see Figure 25Z. Since the first, second, and third electromagnetic waves are orthogonal (ie, non-interfering), they can be transmitted in the same frequency band with no or acceptable small amounts of interference. The combined transmission of three orthogonal electromagnetic wave modes in the same frequency band constitutes a form of mode division multiplexing that provides a means for tripling the information bandwidth. By combining the principles of frequency division multiplexing and wave mode division multiplexing, it is possible to configure the waveguide system in the second In the frequency band, the fourth electromagnetic wave is transmitted using the TM00 wave mode, the fifth electromagnetic wave is transmitted using the HE11 wave mode with horizontal polarization, and the sixth electromagnetic wave is transmitted using the HE11 wave mode with vertical polarization to further increase the bandwidth. It will be appreciated that other types of multiplexing may additionally or alternatively be used with mode division multiplexing without departing from example embodiments.

To illustrate this, assume that each of the three orthogonal electromagnetic waves in the first frequency band supports a transmission bandwidth of 1 GHz. And it is further assumed that each of the three orthogonal electromagnetic waves in the second frequency band also supports a transmission bandwidth of 1 GHz. With three wave modes operating in two frequency bands, an information bandwidth of 6 GHz can be used to transmit communication signals by means of electromagnetic surface waves utilizing these wave modes. With more frequency bands, the bandwidth can be further increased.

It is now assumed that a transmission medium in the form of an insulated conductor (see Fig. 25AA) is used for surface wave transmission. Assume further that the transmission medium has a dielectric layer with a thickness proportional to the radius of the conductor (eg, a conductor with a radius of 4 mm and an insulating layer with a thickness of 4 mm). With this type of transmission medium, a waveguide system can be configured to choose from several options for transmitting electromagnetic waves. For example, the waveguide system may be configured at step 2564 to transmit the first through third electromagnetic waves using mode division multiplexing at a first frequency band (e.g., 1 GHz), and to use electromagnetic waves at a second frequency band (e.g., 2.1 GHz). The third to fourth electromagnetic waves are transmitted by mode division multiplexing, the seventh to ninth electromagnetic waves are transmitted using mode division multiplexing at a third frequency band (for example, 3.2 GHz), and so on. Assuming that each electromagnetic wave supports a bandwidth of 1 GHz, the first to ninth electromagnetic waves can collectively support a bandwidth of 9 GHz.

Alternatively, or concurrently with transmitting electromagnetic waves having orthogonal wave patterns at step 2564, the waveguide system may be configured at step 2564 to transmit one or more high frequency electromagnetic waves (e.g., millimeter waves) on an insulated conductor . In one embodiment, one or more corresponding wave modes that are less susceptible to water films (such as T0m wave mode and EH1m wave mode (where m>0) or HE2m wave mode (where , m>1)) configure the one or more high-frequency electromagnetic waves in non-overlapping frequency bands. In other embodiments, the waveguide system may alternatively be configured to transmit one or more high-frequency electromagnetic waves in non-overlapping frequency bands according to one or more corresponding wave modes that may be vulnerable to water Influenced but nonetheless exhibiting lower propagation losses when the transmission medium is dry, there are longitudinal and/or azimuthal fields near the surface of the transmission medium. The waveguide system can thus be configured to launch several combinations of wave modes on an insulated conductor (and only a dielectric transmission medium, such as a dielectric core) when the insulated conductor is dry.

It is now assumed that a transmission medium in the form of an uninsulated conductor (see FIGS. 25AB to 25AC ) is used for surface wave transmission. Consider further that uninsulated or bare conductors are exposed to environments subjected to various levels of moisture and/or rain (as well as air and atmospheric gases such as oxygen). Uninsulated conductors such as overhead power lines and other uninsulated wires are often made of aluminum sometimes reinforced with steel. Aluminum can react spontaneously with water and/or air to form alumina. The aluminum oxide layer can be relatively thin (eg, nanometer to micrometer thickness). Aluminum oxide layers have dielectric properties and can therefore be used as dielectric layers. Thus, uninsulated conductors can propagate not only the TM00 wave mode, but also other wave modes at high frequencies based at least in part on the thickness of the oxide layer, such as the HE11 wave mode with horizontal polarization, and the HE11 wave mode with vertical polarization . Therefore, an uninsulated conductor with an ambient formed dielectric layer, such as an oxide layer, can be used to transmit electromagnetic waves using both mode division multiplexing and frequency division multiplexing. The subject disclosure contemplates other electromagnetic waves having wave modes (with or without dielectric frequencies) that can propagate across the oxide layer, and these other electromagnetic waves can be applied to the embodiments described in the subject disclosure.

In one embodiment, the term "ambiently formed dielectric layer" may refer to an uninsulated conductor exposed to an environment that cannot be artificially created in a laboratory or other controlled setting (e.g., exposure to air on a utility pole or other exposure environment). , moisture, rain, etc.). In other embodiments, the ambient formed dielectric layer may be formed in a controlled setting, such as exposing the uninsulated conductor to a controlled environment (e.g., controlled moisture or other gaseous substances) manufacturing facilities. In yet another alternative embodiment, the uninsulated conductor can also be "doped" with specific substances/compounds that promote chemical reactions with other substances/compounds available in natural environments or in artificially created laboratories or controlled settings (eg, reactants), resulting in an ambient formed dielectric layer.

Mode division multiplexing and frequency division multiplexing can prove useful in mitigating obstructions such as water accumulating on the outer surface of the transmission medium. To determine whether obstruction mitigation is necessary, the waveguide system may be configured at step 2566 to determine whether obstructions are present on the transmission medium. A film of water (or water droplets) that collects on the outer surface of a transmission medium due to rain, condensation, and/or excess moisture can be a form of obstruction that, if not mitigated, can lead to loss of propagation of electromagnetic waves . Splices of transmission media or other objects coupled to the outer surfaces of the transmission media may also act as obstacles.

Obstacles can be detected by a source waveguide system that emits electromagnetic waves on the transmission medium and measures reflected electromagnetic waves based on these emissions. Alternatively or in combination, the source waveguide system may detect obstacles by receiving communication signals (wireless or electromagnetic waves) from the receiving waveguide system which receives the electromagnetic waves emitted by the source waveguide system and performs quality measurements on them. When an obstacle is detected at step 2566, the waveguide system may be configured to identify options for updating, modifying, or otherwise altering the electromagnetic waves being emitted.

For example, assuming in the case of an insulated conductor, when the insulated conductor is dry, the waveguide system has emitted a higher order wave mode at step 2564, such as the TM01 wave mode with a frequency band starting from 30 GHz with a large bandwidth (e.g., 10 GHz), as shown in Figure 25N shown in . The illustration in FIG. 25N is based on simulations that may not take into account all possible environmental conditions or properties of a particular insulated conductor. Therefore, the TM01 wave mode may have a lower bandwidth than shown. However, for the purpose of illustration, a bandwidth of 10 GHz will be assumed for the electromagnetic wave having the TM01 wave mode.

Although it was pointed out earlier in the subject disclosure that the TM01 wave mode has a desired electric field alignment that is non-longitudinal and non-azimuthal near the outer surface, the wave mode will still experience certain Signal attenuation, which in turn reduces its operating bandwidth. This attenuation is demonstrated in Figure 25N, which shows electromagnetic waves in the TM01 wave mode with a bandwidth of about 10 GHz (30 GHz to 40 GHz) on a dry insulated conductor, which drops to about 1 GHz (30 GHz to 31 GHz) when the insulated conductor is wet bandwidth. To mitigate bandwidth loss, waveguide systems can be configured to transmit electromagnetic waves at much smaller frequencies (eg, less than 6 GHz) using mode division multiplexing and frequency division multiplexing.

For example, the waveguide system may be configured to emit a first set of electromagnetic waves; specifically, a first electromagnetic wave having a TM00 wave mode, a second electromagnetic wave having a HE11 wave mode with horizontal polarization, and a HE11 wave having a vertical polarization The third electromagnetic wave of the mode, each electromagnetic wave has a center frequency at 1 GHz. Assuming that the available frequency band from 500 MHz to 1.5 GHz is used to transmit communication signals, each electromagnetic wave can provide a bandwidth of 1 GHz and collectively provide a system bandwidth of 3 GHz.

Assume also that the waveguide system is configured to transmit a second set of electromagnetic waves; specifically, a fourth electromagnetic wave having a TM00 wave mode, a fifth electromagnetic wave having a HE11 wave mode having horizontal polarization, and a fifth electromagnetic wave having a HE11 wave mode having vertical polarization The sixth electromagnetic wave, each having a center frequency at 2.1 GHz. Assuming a frequency band from 1.6GHz to 2.6GHz, with a guard band of 100MHz between the first group of electromagnetic waves and the second group of electromagnetic waves, each electromagnetic wave can provide a bandwidth of 1GHz, and together provide an additional bandwidth of 3GHz, thus providing now up to 6GHz system bandwidth.

Assume further that the waveguide system is also configured to emit a third set of electromagnetic waves; specifically, a seventh electromagnetic wave having a TM00 wave mode, an eighth electromagnetic wave having a HE11 wave mode with horizontal polarization, and an HE11 wave having vertical polarization The ninth electromagnetic wave of the mode, each having a center frequency at 3.2 GHz. Assuming a frequency band from 2.7GHz to 3.7GHz, with a guard band of 100MHz between the second group of electromagnetic waves and the third group of electromagnetic waves, each electromagnetic wave can provide a bandwidth of 1GHz, and together provide an additional bandwidth of 3GHz, thus providing now up to 9GHz system bandwidth.

The combination of the TM01 wave mode and these three sets of electromagnetic waves configured for mode division multiplexing and frequency division multiplexing provides a total system bandwidth of 10 GHz, whereby when a high frequency electromagnetic wave with the TM01 wave mode propagates on a dry insulated conductor Restores the previously available 10GHz of bandwidth. FIG. 25AD illustrates a process for performing mitigation on a TM01 wave mode subject to an obstacle, such as the water film detected at step 2566 . 25AD illustrates the transition from a dry insulated conductor supporting a high bandwidth TM01 wave mode to a moist insulated conductor supporting a lower bandwidth TM01 wave mode with a wave mode division multiplexing (WMDM) scheme It is combined with the low-frequency TM00 wave mode and HE11 wave mode configured by the frequency division multiplexing (FDM) scheme to restore the loss of system bandwidth.

Consider now an uninsulated conductor in which the waveguide system has launched at step 2564 a TM00 wave mode with a frequency band starting at 10 GHz with a large bandwidth (eg, 10 GHz). Assume now that the transmission medium propagating the 10 GHz TM00 wave mode is exposed to obstacles such as water. As noted earlier, high frequency TM00 wave modes on insulated conductors experience substantial signal attenuation (e.g., 45dB/M at 10GHz - see Figure 25J). Similar attenuation will exist for 10 GHz (or higher) TM00 wave modes propagating on "uninsulated" conductors. However, environmentally exposed uninsulated conductors (eg, aluminum) may have an oxide layer formed on the outer surface, which may serve as a dielectric layer to support wave modes other than TM00 (eg, HE11 wave mode). It should be further noted that at lower frequencies, TM00 wave modes propagating on insulated conductors exhibit much lower attenuation (eg, 0.62dB/M at 4GHz - see Figure 25J). TM00 wave modes operating at less than 6 GHz will similarly exhibit lower propagation losses on uninsulated conductors. Therefore, to mitigate bandwidth loss, the waveguide system can be configured to transmit electromagnetic waves with the TM00 wave mode at lower frequencies (e.g., 6 GHz or less) and at higher frequencies with HE11 waves configured for WMDM and FDM. Pattern of electromagnetic waves.

Referring back to FIG. 25Y, assume then that the waveguide system detects an obstruction, such as water, at step 2566 on an environmentally exposed uninsulated conductor. The waveguide system may be configured to mitigate obstacles by emitting a first electromagnetic wave configured with a TM00 wave mode having a center frequency at 2.75 GHz. Assuming that the available frequency band from 500 MHz to 5.5 GHz is used to transmit communication signals, electromagnetic waves can provide a system bandwidth of 5 GHz.

Figure 25AF provides a graphical representation of the electric field plot for the HE11 wave mode at 200 GHz on a bare conductor with a thin aluminum oxide layer (4um). The graph indicates the magnitude of the field strength at the point in time when the magnitude of the field strength of the rho, z and phi field components is at its peak value, as the radial distance from the center of the bare conductor function. Although the field strengths are calculated based on the absence of water, starting from the outer surface of the oxide layer and passing through the location that would be occupied by the water film, the z and phi field components of the electric field can have magnitudes relative to the radial rho field Field strengths with very small values, as shown in Fig. 25AF.

Assuming that the oxide layer or other dielectric layer is comparable in size to that in the graph of FIG. Three electromagnetic waves, each having a center frequency at 200 GHz (other lower or higher center frequencies may be used). Assuming further that each electromagnetic wave is respectively configured according to an HE vertically polarized wave pattern and an HE horizontally polarized wave pattern having a bandwidth of 2.5 GHz, these waves together provide an additional bandwidth of 5 GHz. By combining the low-frequency TM00 wave pattern with the high-frequency HE wave pattern, the system bandwidth can be restored to 10 GHz. It will be appreciated that HE wave modes at other center frequencies and bandwidths may be possible depending on the thickness of the oxide layer, the properties of the uninsulated conductor, and/or other environmental factors.

25AE illustrate a process for performing mitigation on high frequency TM00 wave patterns subject to obstructions such as the water film detected at step 2566 . Figure 25AD illustrates the transition from a dry uninsulated conductor supporting a high bandwidth TM00 wave mode to a wet uninsulated conductor that combines the low frequency TM00 wave mode with the high frequency HE11 wave mode configured according to the WMDM scheme and the FDM scheme combined to recover the loss of system bandwidth.

It will be appreciated that the mitigation techniques described above are non-limiting. For example, the above-mentioned center frequency may vary between systems. Also, the raw wave pattern used before an obstacle is detected may be different from the above description. For example, in the case of an insulated conductor, the EH11 wave mode can be used alone or in combination with the TM01 wave mode. It should also be understood that WMDM techniques and FDM techniques can be used to transmit electromagnetic waves all the time, not just when an obstacle is detected at step 2566 . It will be further understood that other wave modes that may support WMDM techniques and/or FDM techniques may be applied to and/or combined with the embodiments described in the subject disclosure and are thus contemplated by the subject disclosure .

Referring back to FIG. 25Y , once a mitigation scheme using WMDM and/or FDM has been determined in accordance with the above description, the waveguide system at step 2568 may be configured to notify one or more other waveguide systems that it is intended to be used at step 2570 Update the mitigation scheme for one or more electromagnetic waves before performing the update. If the signal degradation in the electromagnetic waves is too severe, the notification can be sent wirelessly to one or more other waveguide systems using the antenna. If the signal attenuation is tolerable, the notification may be sent via the affected electromagnetic waves. In other embodiments, the waveguide system may be configured to skip step 2568 and perform the mitigation scheme using WMDM and/or FDM at step 2570 without notification. This embodiment is applicable eg where the other receive waveguide system(s) know in advance which mitigation scheme(s) will be used, or where the receive waveguide system(s) are configured to use signal detection techniques to discover mitigation schemes. Once the mitigation scheme using WMDM and/or FDM has been initiated at step 2570, the waveguide system may continue to process received communication signals at steps 2562 and 2564 as described earlier using the updated configuration of electromagnetic waves.

At step 2566, the waveguide system may monitor whether the obstacle is still present. This determination can be made by sending a test signal (e.g., electromagnetic surface waves in the original wave mode) to the other waveguide system(s) and waiting for test results back from the waveguide system(s) if the situation has improved, and/or by using a method such as Other obstacle detection techniques such as signal reflection testing based on transmitted test signals are performed. Once it is determined that the obstruction has been removed (eg, the transmission medium has dried out), the waveguide system may proceed to step 2572 and determine that a signal update was performed at step 2568 using WMDM and/or FDM as a mitigation technique. The waveguide system may then be configured to notify the receiving waveguide system(s) of the intention to restore the transmission to the original wave mode at step 2568, or bypass this step and proceed to step 2570, in a later step, the The described waveguide system restores the transmission to the original wave mode and assumes that the receiving waveguide system(s) knows the original wave mode and the corresponding transmission parameters, or can otherwise detect this change.

The waveguide system may also be adapted to receive electromagnetic waves configured for WMDM and/or FDM. For example, assume that an electromagnetic wave with a high bandwidth (eg, 10 GHz) TM01 wave mode is propagating on an insulated conductor as shown in Figure 25AD, and that the electromagnetic wave is generated by a source waveguide system. At step 2582, the receive waveguide system may be configured to normally process a single electromagnetic wave having a TM01 wave mode. However, assume that the source waveguide system is converted to emit electromagnetic waves using WMDM and FDM on insulated conductors along with the lower bandwidth TM01 wave mode, as previously described in Figure 25AD. In this instance, the receiving waveguide system would have to handle multiple electromagnetic waves with different wave modes. Specifically, the receive waveguide system at step 2582 will be configured to selectively process each of the first through ninth electromagnetic waves using WMDM and FDM and the electromagnetic wave using the TM01 wave mode as shown in FIG. 25AD.

Once the one or more electromagnetic waves have been received at step 2582, the receiving waveguide may be configured to use signal processing techniques to obtain ) Communication signals carried by electromagnetic wave(s) generated at . At step 2586, the receiving waveguide system may also determine whether the source waveguide system has updated the transmission scheme. The update may be detected from data provided in electromagnetic waves emitted by the source waveguide system or from wireless signals emitted by the source waveguide system. If there is no update, the receiving waveguide system may continue to receive and process electromagnetic waves at steps 2582 and 2584 as previously described. However, if an update is detected at step 2586, the receiving waveguide system may proceed to step 2588 to coordinate the update with the source waveguide system and thereafter receive and process the updated electromagnetic wave at steps 2582 and 2584 as previously described .

It will be appreciated that method 2560 may be used with any communication scheme, including simplex and duplex communication between waveguide systems. Thus, a source waveguide system that performs updates according to other wave modes for transmitting electromagnetic waves will in turn cause a receiving waveguide system to perform similar steps for return electromagnetic wave transmission. It will also be appreciated that the above-described embodiments associated with method 2560 of FIG. 25Y and the embodiments shown in FIGS. 25Z-25AE may be combined, in whole or in part, with other embodiments of the subject disclosure for use in The purpose of mitigating propagation losses caused by obstacles at or near the outer surface of a transmission medium (eg, an insulated conductor, an uninsulated conductor, or any transmission medium with an outer dielectric layer). Obstacles may be liquids (eg, water), solid objects (eg, ice, snow, splices, tree branches, etc.) disposed on the outer surface of the transmission medium, or any other objects located at or near the outer surface of the transmission medium.

Although the corresponding process is shown and described as a series of blocks in FIG. 25Y for purposes of simplicity of illustration, it should be understood and appreciated that claimed subject matter is not limited by the order of the blocks, as some methods The blocks may occur in a different order and/or concurrently with other blocks than depicted and described herein. Moreover, not all illustrated blocks may be required to implement the methodologies described below.

Referring now to FIGS. 25AG and 25AH , block diagrams illustrating example non-limiting embodiments for transmitting orthogonal wave patterns according to the method 2560 of FIG. 25Y are shown. 25AG depicts an embodiment for simultaneously transmitting a TM00 wave pattern, a HE11 wave pattern with vertical polarization, and a HE11 wave pattern with horizontal polarization, as shown in the time instance in FIG. 25Z. In one embodiment, a waveguide launch station with eight (8) MMICs located in symmetrical locations (e.g., north, northeast, east, southeast, south, southwest, west, and northwest) as shown in FIG. These orthogonal wave patterns are emitted. The waveguide launch station of Figure 18R (or Figure 18T) can be configured with these 8 MMICs. Additionally, a waveguide launch pad may be configured with a cylindrical sleeve 2523A and tapered dielectric wrapped around a transmission medium (eg, an insulated conductor, an uninsulated conductor, or other cable having a dielectric layer such as a dielectric core). A housing assembly (not shown) of the waveguide launch pad may be configured to include a mechanism (eg, a hinge) for enabling the longitudinal opening of the waveguide launch pad to be placed and latched around the circumference of the transmission medium.

With these configurations in mind, the waveguide launch station may include three transmitters (TX1, TX2, and TX3) coupled to the MMIC (see Figures 25AG and 18W) with respective coordinate positions. The interconnectivity between the transmitters (TX1, TX2 and TX3) and the MMICs can be implemented using a common printed circuit board or other suitable interconnection technology. The first transmitter (TX1) can be configured to transmit the TM00 wave pattern, the second transmitter (TX2) can be configured to transmit the HE11 vertically polarized wave pattern, and the third transmitter (TX3) can be configured to transmit Transmit HE11 horizontally polarized wave mode.

A first signal port (shown as "SP1") of a first transmitter (TX1) may be coupled in parallel to each of the 8 MMICs. A second signal port (shown as "SP2") of the first transmitter (TX1) may be coupled to a conductive sleeve 2523A placed on the transmission medium by a waveguide launch station as described above. The first transmitter (TX1) may be configured to receive the first set of communication signals described in step 2562 of Figure 25Y. The first set of communication signals may be frequency shifted (if required) from their natural frequencies by the first transmitter (TX1) for orderly placing the communication signals in the channel of the first electromagnetic wave configured according to the TM00 wave pattern middle. The 8 MMICs coupled to the first transmitter (TX1) may be configured to upconvert (or downconvert) the first set of communication signals to the same center frequency (e.g., for the first Electromagnetic wave is 1GHz). All 8 MMICs will have a synchronous reference oscillator that can be phase locked using various synchronization techniques.

Since the 8 MMICs receive signals from the first signal port of the first transmitter (TX1) based on the reference provided by the second signal port, the 8 MMICs receive signals with the same polarity. Thus, once the signals have been upconverted (or downconverted) and processed by the 8 MMICs for transmission, the antenna or antennas of each of the 8 MMICs simultaneously radiate electric fields of the same polarity. Signal. Collectively, MMICs that are located opposite each other (e.g., MMIC North and MMIC South) will have electric field structures aligned towards or away from the transmission medium, producing at certain moments an outward field like the TM00 wave pattern shown in Figure 25Z structure. Due to the constant oscillatory nature of the signals radiated by these 8 MMICs, it will be understood that at other times the field structure shown in Figure 25Z will radiate inwards. By symmetrically radiating electric fields with the same polarity, the collection of MMICs on the contrary helps to induce a first electromagnetic wave with a TM00 wave mode, which propagates on a transmission medium with a dielectric layer and can transmit a first set of communication signals to the receiving waveguide system.

Turning now to the second transmitter (TX2) in FIG. 25AG, this transmitter has a first signal port (SP1) coupled to the MMIC at the north, northeast, and northwest locations, while the second transmitter (TX2) The second signal port (SP2) is coupled to the MMICs at the south, southeast and southwest locations (see Figure 18W). The second transmitter (TX2) may be configured to receive a second set of communication signals described in step 2562 of FIG. 25Y that is different from the first set of communication signals received by the first transmitter (TX1). communication signal. The second set of communication signals may be frequency shifted (if desired) from their natural frequencies by the second transmitter (TX2) for orderly placing the communication signals in a configuration according to the HE11 wave pattern with vertical polarization. In the channel of the second electromagnetic wave. These 6 MMICs coupled to the second transmitter (TX2) can be configured to upconvert (or downconvert) the second set of communication signals to the same center frequency as used for the TM00 wave mode (i.e., as described with respect to FIG. 25AD 1GHz as described). Since the TM00 wave mode is orthogonal to the HE11 wave mode with vertical polarization, they can share the same center frequency in overlapping frequency bands without interference.

Referring back to FIG. 25AG, the first signal port (SP1) of the second transmitter (TX2) generates a signal of opposite polarity to the signal of the second signal port (SP2). Therefore, the polarity of the electric field alignment for signals generated by the antenna or antennas of the northern MMIC will be opposite to that of the electric field alignment for signals generated by the antenna or antennas of the southern MMIC. Therefore, the electric fields of the northern and southern MMICs will have electric field structures vertically aligned in the same direction, resulting in a northern field structure at some point with a vertically polarized HE11 wave mode as shown in Figure 25Z. Due to the constant oscillatory nature of the signals radiated by the northern and southern MMICs, it will be understood that at other times the HE11 wave pattern will have a southern field structure. Similarly, based on the opposite polarity of the signals provided by the first and second signal ports respectively to the northeast and southeast MMICs, these MMICs will at some point generate the HE11 wave with vertical polarization depicted in Figure 25Z The east side of the mode shows the curved electric field structure. Also, based on the opposite polarity of the signals provided to the Northwest and Southwest MMICs, these MMICs will at some point generate the curved electric field structure shown on the west side of the HE11 wave pattern with vertical polarization depicted in Figure 25Z.

By radiating electric fields with opposite polarities from opposite MMICs (North, Northeast, and Northwest vs. South, Southeast, and Southwest), signal ensembles with directionally aligned field structures help induce The HE11 wave pattern is the second electromagnetic wave. The second electromagnetic wave propagates along the "same" transmission medium as previously described for the first transmitter (TX1). Considering the orthogonality of the TM00 wave mode to the HE11 wave mode with vertical polarization, there would ideally be no interference between the first electromagnetic wave and the second electromagnetic wave. Accordingly, first and second electromagnetic waves having overlapping frequency bands propagating along the same transmission medium can successfully transmit the first set of communication signals and the second set of communication signals to the same (or other) receiving waveguide system.

Turning now to the third transmitter (TX3) in FIG. 25AG, this transmitter has a first signal port (SP1) coupled to the MMIC located at the east, northeast, and southeast locations, while the third transmitter (TX3) The second signal port (SP2) is coupled to the MMICs at the west, northwest and southwest locations (see Figure 18W). The third transmitter (TX3) may be configured to receive a third set of communication signals described in step 2562 of FIG. The first group of communication signals and the second group of communication signals received by the device (TX2). The third group of communication signals may be frequency shifted (if required) from their natural frequency by a third transmitter (TX3) for orderly placing the communication signals in a configuration according to the HE11 wave pattern with horizontal polarization. In the channel of the second electromagnetic wave. These 6 MMICs coupled to the third transmitter (TX3) can be configured to upconvert (or downconvert) the third set of communication signals to the same Center frequency (ie, 1 GHz as described with respect to Figure 25AD). Since the TM00 wave mode, the HE11 wave mode with vertical polarization, and the HE11 wave mode with horizontal polarization are orthogonal, they can share the same center frequency in overlapping frequency bands without interference.

Referring back to FIG. 25AG, the first signal port (SP1) of the third transmitter (TX3) generates a signal having an opposite polarity to the signal of the second signal port (SP2). Therefore, the polarity of the electric field alignment for signals generated by the antenna(s) of the eastern MMIC will be opposite to the polarity of the electric field alignment for signals generated by the antenna(s) of the western MMIC. Therefore, the electric fields of the eastern and western MMICs will have electric field structures aligned horizontally in the same direction, resulting in a western field structure at some point with a horizontally polarized HE11 wave mode as shown in Figure 25Z. Due to the constant oscillatory nature of the signals radiated by the eastern and western MMICs, it will be understood that at other times the HE11 wave pattern will have an eastern field structure. Similarly, based on the opposite polarity of the signals provided by the first and second signal ports respectively to the NE and NW MMICs, these MMICs will at some point generate the HE11 wave with horizontal polarization depicted in Figure 25Z The curved electric field structure is shown on the north side of the model. Also, based on the opposite polarity of the signals provided to the SE and SW MMICs, these MMICs will at some point generate the curved electric field structure shown on the south side of the HE11 wave pattern with horizontal polarization depicted in Figure 25Z.

By radiating electric fields with opposite polarities from opposite MMICs (east, northeast, and southeast vs. west, northwest, and southwest), signal ensembles with directionally aligned field structures help to induce The HE11 wave pattern is the third electromagnetic wave. The third electromagnetic wave propagates along the "same" transmission medium as previously described for the first transmitter (TX1) and the second transmitter (TX2). Considering the orthogonality of the TM00 wave mode, the HE11 wave mode with vertical polarization and the HE11 wave mode with horizontal polarization, ideally there will be no interference between the first, second and third electromagnetic waves. Therefore, the first electromagnetic wave, the second electromagnetic wave and the third electromagnetic wave with overlapping frequency bands propagating along the same transmission medium can successfully transmit the first group of communication signals, the second group of communication signals and the third group of communication signals to the same (or other) Receive waveguide system.

Due to the orthogonality of the electromagnetic waves described above, the receiving waveguide system can be configured to selectively retrieve the first electromagnetic wave with the TM00 wave mode, the second electromagnetic wave with the HE11 wave mode with vertical polarization, and the The third electromagnetic wave of the HE11 wave pattern. After processing each of the electromagnetic waves, the receiving waveguide system may be further configured to obtain the first set of communication signals, the second set of communication signals and the third set of communication signals conveyed by the electromagnetic waves. 25AH illustrates a block diagram for selectively receiving each of a first electromagnetic wave, a second electromagnetic wave, and a third electromagnetic wave.

Specifically, the signal received by all 8 MMICs and the signal reference provided by the metal sleeve 2523A can be taken by the first receiver (RX1) shown in FIG. 25AH as depicted in the block diagram in FIG. 25AI. The difference between them is used to selectively receive the first electromagnetic wave having the TM00 wave mode. The signals received by the MMICs at the north, northeast, and northwest locations can be compared with the signals received by the MMICs at the south, southeast, and southeast locations as depicted in the block diagram in FIG. 25AJ by the second receiver (RX2) shown in FIG. The difference between the signals received by the MMICs at the Southwest and Southwest locations to selectively receive a second electromagnetic wave with a vertically polarized HE11 wave pattern. The third receiver (RX3) shown in FIG. 25AH can be obtained by taking the signals received by the MMICs located in the east, northeast, and southeast locations as depicted in the block diagram in FIG. The difference between the signals received by the MMICs at the northwest and southwest locations is used to selectively receive a third electromagnetic wave having a horizontally polarized HE11 wave pattern.

Figure 25AL illustrates a simplified functional block diagram of the MMIC. For example, a MMIC may utilize a mixer coupled to a reference (TX) oscillator that will be driven by one of the signal ports (SP1 or one of the communication signals provided by SP2) to the desired center frequency. For example, in the case of TX1, communication signals from SP1 are provided to the transmission paths of each of the MMICs (ie, NE, NW, SE, SW, N, S, E, and W). In the case of TX2, the communication signal from SP1 is provided to another transmit path of the three MMICs (ie, N, E and NW). Note that the transmission path used by the MMICs N, E, and W for the communication signal provided by SP1 of TX2 is different from the transmission path used by the MMIC for the communication signal provided by SP1 of TX1. Similarly, communication signals from SP2 of TX2 are provided to another transmit path of three other MMICs (ie, S, SE and SW). Again, the transmission paths used by the MMICs S, SE and SW for communication signals provided by SP2 of TX2 are different from the transmission paths used by the MMICs for communication signals from SP1 of TX1 and SP1 of TX2. Finally, in the case of TX3, the communication signal from SP1 is provided to yet another transmit path of the three MMICs (ie, E, NE and SE). Note that the transmission paths used by the MMICs E, NE, and SE for communication signals from SP1 of TX3 are different from those used by the MMICs for communication signals provided by SP1 of TX1, SP1 of TX2, and SP2 of TX2. Similarly, communication signals from SP2 of TX3 are provided to another transmit path of three other MMICs (ie, W, NW, and SW). Again, the transmit path used by MMIC W, NW, and SW for communication signals provided by SP2 of TX3 is the same as the transmit path used by MMIC for communication signals from SP1 of TX1, SP1 of TX2, SP2 of TX2, and SP1 of TX3 different.

Once the communication signal has been frequency shifted by the mixer shown in the transmit path, the frequency shifted signal generated by the mixer can be filtered by a bandpass filter that removes spurious signals. The output of the bandpass filter may in turn be provided to a power amplifier coupled to an antenna through a duplexer for radiating the signal in the manner previously described. The duplexer can be used to isolate the transmit path from the receive path. The illustration of Figure 25AL is intentionally oversimplified for ease of illustration.

It will be appreciated that the subject disclosure contemplates other components (not shown), such as impedance matching circuits, phase locked loops, or other suitable components for improving the accuracy and efficiency of the transmit path (and receive path). Furthermore, while a single antenna may be implemented by each MMIC, other designs with multiple antennas are equally possible. It should be further understood that in order to achieve more than one orthogonal wave mode with overlapping frequency bands (e.g., TM00 wave mode, HE11 vertical wave mode, and HE11 horizontal wave mode as described above), the same reference oscillator can be used to repeat N transmissions path. N may represent an integer associated with the number of instances of the MMIC used to generate each wave pattern. For example, in FIG. 25AG, the MMIC NE is used three times; therefore, the MMIC NE has three transmit paths (N=3), and the MMIC NW is used three times; therefore, the MMIC NW has three transmit paths (N=3), and the MMIC N is Used twice; therefore, MMIC N has two transmit paths (N=2), and so on. If frequency division multiplexing is used to generate the same wave pattern in other frequency band(s) (see Figure 25AD and Figure 25AE), then different reference(s) centered on other frequency band(s) can further be used oscillator to repeat the emission path.

In the receive path shown in FIG. 25AL, N signals provided by N antennas via the duplexers of each transmit path in the MMIC can be filtered by corresponding N band-pass filters that provides its output to N low noise amplifiers. The N low noise amplifiers in turn provide their signals to N mixers to generate N intermediate frequency received signals. As mentioned earlier, N represents the number of instances of the MMIC used to receive wireless signals of different wave patterns. For example, in Figure 25AH, MMIC NE is used in three instances; therefore, MMIC NE has three receive paths (N=3), and MMIC N is used in two instances; therefore, MMIC N has two receive paths (N=2), and so on.

Referring back to FIG. 25AL, to reconstruct the wave mode signal, Y received signals provided by the receive paths of some MMICs are subtracted from X received signals provided by other MMICs based on the configuration shown in FIGS. 25AI to 25AK (or reference from metal sleeve 2523A of Figure 25D). For example, by providing the received signals of all MMICs (NE, NW, SE, SW, N, S, E, W) to the positive port of the adder (i.e., the X signal), while feeding the metal sleeve from FIG. 25D The reference signal of 2523A is provided to the negative port of the adder (ie, the Y signal) to reconstruct the TM00 signal - see Fig. 25AI. The difference between the X signal and the Y signal produces the TM00 signal. To reconstruct the HE11 vertical signal, the received signals of MMIC N, NE, and NW are provided to the positive port of the adder (i.e., the X signal), while the received signals of MMIC S, SE, and SW are provided to the negative port of the adder (ie, Y signal) - See Figure 25AJ. The difference between the X signal and the Y signal produces the HE11 vertical signal. Finally, to reconstruct the HE11 level signal, the received signals of MMIC E, NE, and SE are provided to the positive port of the adder (i.e., the X signal), while the received signals of MMIC W, NW, and SW are provided to the adder's Negative port (ie, Y signal) - see Figure 25AK. The difference between the X signal and the Y signal produces the HE11 level signal. Since there are three wave-mode signals to be reconstructed, the block diagram of the adder with X and Y signals is repeated three times.

Each of these reconstructed signals is at an intermediate frequency. These intermediate frequency signals are provided to receivers (RX1, RX2, and RX3) that include circuitry (eg, DSP, A/D converter, etc.) for processing the intermediate frequency signals and selectively deriving communication signals therefrom. Similar to the transmit path, the reference oscillators of the three receiver paths may be configured to be synchronized using phase locked loop techniques or other suitable synchronization techniques. If frequency division multiplexing is used for the same wave pattern in other frequency band(s) (see Figure 25AD and Figure 25AE), the receiver can further be duplicated using a different reference oscillator centered on the other frequency band(s) path.

It will be appreciated that other suitable designs, which may be used as alternatives to the embodiment shown in Figures 25AG-25AL, may be used to transmit and receive orthogonal wave patterns. For example, there may be fewer or more MMICs than described above. Instead of MMICs or in combination, slotted launch pads as shown in Figures 18N-18O, 18Q, 18S, 18U and 18V may be used. It should be further understood that more or less complex functional components may be used to transmit or receive orthogonal wave patterns. Accordingly, the subject disclosure contemplates other suitable designs and/or functional components for transmitting and receiving orthogonal wave patterns.

Referring now to FIG. 26 , illustrated therein is a block diagram of a computing environment in accordance with various aspects described herein. In order to provide additional context for various embodiments of the embodiments described herein, FIG. 26 and the following discussion are intended to provide a brief general description of a suitable computing environment 2600 in which embodiments of the subject disclosure may be implemented. Although embodiments have been described above in the general context of computer-executable instructions that can run on one or more computers, those skilled in the art will appreciate that the described embodiments can also be combined with other program modules and/or Implemented as a combination of hardware and software.

Generally, program modules include routines, programs, components, data structures, etc. that perform particular tasks or implement particular abstract data types. Moreover, those skilled in the art will recognize that the inventive methods described may be practiced with other computer system configurations, including single-processor or multi-processor computer systems, minicomputers, mainframe computers, as well as personal computers, handheld computing devices, Microprocessor-based or programmable consumer electronics, etc., each of which is operatively coupled to one or more associated devices.

As used herein, processing circuitry includes processors as well as other special purpose circuitry such as application specific integrated circuits, digital logic circuits, state machines, programmable gate arrays, or other circuits. It should be noted that although any functions and features described herein in connection with the operation of a processor may equally be performed by processing circuitry.

Unless the context clearly dictates otherwise, the terms "first", "second", "third", etc. as used in the claims are for clarity only and do not otherwise indicate or imply any temporal order. For example, "first determination," "second determination," and "third determination" do not indicate or imply that the first determination was made before the second determination, or vice versa, and so on.

The illustrated embodiments of the embodiments herein may also be practiced in distributed computing environments where certain tasks are performed by remote processing devices that are linked through a communications network. In a distributed computing environment, program modules may be located in both local and remote memory storage devices.

Computing devices typically include a wide variety of media, which may include computer-readable storage media and/or communication media, both terms are used differently from one another herein as follows. Computer readable storage media can be any available storage media that can be accessed by a computer and includes both volatile and nonvolatile media, removable and non-removable media. By way of example, and not limitation, a computer readable storage medium may be implemented in conjunction with any method or technology for storage of information such as computer readable instructions, program modules, structured data, or unstructured data.

Computer-readable storage media may include, but are not limited to, random access memory (RAM), read-only memory (ROM), electrically erasable programmable read-only memory (EEPROM), flash memory or other memory technologies, compact disc read-only memory (CD - ROM), digital versatile disk (DVD) or other optical disk storage, magnetic tape cartridge, magnetic tape, magnetic disk storage or other magnetic storage device or other tangible and/or non-transitory media that may be used to store desired information. In this regard, the terms "tangible" or "non-transitory" as applied herein to storage, memory, or computer-readable media should be understood as modifiers excluding per se the propagation of only transient signals and Rights to all standard storage devices, memories, or computer-readable media that by themselves do not merely propagate transient signals are not waived.

Computer-readable storage media may be accessed by one or more local or remote computing devices, eg, via access requests, queries, or other data retrieval protocols, for a variety of operations with respect to the information stored by the media.

Communication media typically embodies computer readable instructions, data structures, program modules or other structured or unstructured data in a data signal such as a modulated data signal (e.g., a carrier wave or other transport mechanism) and includes any information delivery or transmission media . The term "modulated data signal" or signal means a signal that has one or more of its characteristics set or changed in such a manner as to encode information in the signal or signals. By way of example, and not limitation, communication media includes wired media such as a wired network or direct-wired connection, and wireless media such as acoustic, RF, infrared and other wireless media.

Referring again to FIG. 26, an example environment 2600 is used to transmit and receive signals via a base station (e.g., base station equipment 1504, macrocell site 1502, or base station 1614) or a central office (e.g., central office 1501 or 1611), or to form At least a portion of said base station or central office. At least a portion of the example environment 2600 may also be used with the transmitting device 101 or 102 . The example environment may include a computer 2602 including a processing unit 2604 , a system memory 2606 and a system bus 2608 . System bus 2608 couples system components including but not limited to system memory 2606 to processing unit 2604 . The processing unit 2604 may be any of various commercially available processors. Dual microprocessors and other multi-processor architectures may also be used as processing unit 2604 .

The system bus 2608 can be any of several types of bus structures, which can further interconnect to a memory bus (with or without a memory controller) using any of a variety of commercially available bus architectures , peripheral bus and local bus. System memory 2606 includes ROM 2610 and RAM 2612 . A Basic Input/Output System (BIOS) may be stored in non-volatile memory such as ROM, Erasable Programmable Read-Only Memory (EPROM), EEPROM, etc., where the BIOS contains among the elements within the computer 2602 that help The basic routine for passing information between. RAM 2612 may also include high-speed RAM, such as static RAM for caching data.

The computer 2602 also includes an internal hard disk drive (HDD) 2614 (e.g., EIDE, SATA), which may also be configured for external use in a suitable enclosure (not shown), the computer also includes Magnetic floppy disk drive (FDD) 2616 (e.g., to read from or write to removable disk 2618) and optical disk drive 2620 (e.g., to read CD-ROM disk 2622, or to read from other high-capacity optical media such as DVD fetch or write to it). Hard disk drive 2614, magnetic disk drive 2616, and optical disk drive 2620 may be connected to system bus 2608 through hard disk drive interface 2624, magnetic disk drive interface 2626, and optical drive interface 2628, respectively. The interface 2624 for external driver implementation includes at least one or both of Universal Serial Bus (USB) and Institute of Electrical and Electronics Engineers (IEEE) 1394 interface technologies. Other external drive connection technologies are within contemplation of the embodiments described herein.

The drives and their associated computer-readable storage media provide non-volatile storage of data, data structures, computer-executable instructions, and the like. For the computer 2602, the drives and storage media accommodate the storage of any data in a suitable digital format. While the above description of computer-readable storage media refers to hard disk drives (HDDs), removable magnetic disks, and removable optical media such as CDs or DVDs, those skilled in the art will recognize that other types of computer-readable storage media Media (such as zip drives, magnetic tape cartridges, flash memory cards, magnetic tape cartridges, etc.) may also be used in the example operating environment, and additionally any such storage media may contain computer-executable instructions for performing the methods described herein.

A number of program modules may be stored in drives and RAM 2612 , including operating system 2630 , one or more application programs 2632 , other program modules 2634 , and program data 2636 . All or portions of the operating system, applications, modules, and/or data may also be cached in RAM 2612 . The systems and methods described herein can be implemented using various commercially available operating systems or combinations of operating systems. Examples of applications 2632 that may be implemented by the processing unit 2604 and otherwise executed include diversity selection determinations performed by the transmission device 101 or 102 .

A user may enter commands and information into computer 2602 through one or more wired/wireless input devices (eg, keyboard 2638 and pointing device such as mouse 2640 ). Other input devices (not shown) may include microphones, infrared (IR) remote controls, joysticks, game pads, stylus, touch screens, and the like. These and other input devices are often connected to processing unit 2604 through input device interface 2642, which may be coupled to system bus 2608, but may be connected through other interfaces, such as parallel ports, IEEE 1394 serial ports, game ports, general purpose serial Bus (USB) port, IR interface, etc.

A monitor 2644 or other type of display device may also be connected to the system bus 2608 via an interface such as a video adapter 2646 . It will also be appreciated that in alternative embodiments, the monitor 2644 can also be any display device (e.g., another computer with a display, a smart phone, a tablet, etc.) for viewing via any means of communication, including via the Internet and based on Cloud's network) receives display information associated with computer 2602. In addition to monitor 2644, computers typically include other peripheral output devices (not shown), such as speakers, printers, and the like.

Computer 2602 may operate in a networked environment using logical connections via wired and/or wireless communications to one or more remote computers, such as remote computer(s) 2648 . The remote computer(s) 2648 may be a workstation, server computer, router, personal computer, portable computer, microprocessor-based entertainment device, peer-to-peer device, or other public network node, and typically includes Many or all of the elements are described, but only memory/storage 2650 is shown for brevity. Logical connections depicted include wired/wireless connections to a local area network (LAN) 2652 and/or larger networks (eg, wide area network (WAN) 2654 ). Such LAN and WAN networking environments are commonplace in offices and corporations and facilitate enterprise-wide computer networks (such as intranets), all of which can be connected to a global communications network (eg, the Internet).

When used in a LAN networking environment, the computer 2602 can be connected to a local network 2652 through a wired and/or wireless communication network interface or adapter 2656 . The adapter 2656 may facilitate wired or wireless communication to the LAN 2652, which may also include a wireless AP deployed thereon for communicating with the wireless adapter 2656.

When used in a WAN networking environment, the computer 2602 may include a modem 2658 or may be connected to a communication server over the WAN 2654, or have other means for establishing communications over the WAN 2654 (such as through the Internet). A modem 2658 , which may be an internal or external device and a wired or wireless device, may be connected to the system bus 2608 via an input device interface 2642 . In a networked environment, program modules depicted relative to the computer 2602 , or portions thereof, may be stored in the remote memory/storage device 2650 . It will be appreciated that the network connections shown are examples and other means of establishing a communications link between the computers may be used.

The computer 2602 is operable to communicate with any wireless device or entity operatively deployed in wireless communication, such as printers, scanners, desktop and/or portable computers, portable data assistants, communication satellites, any Equipment or locations (eg, kiosks, newsstands, restrooms) with which tags are associated can be detected, as well as telephones. This can include wireless fidelity (Wi-Fi) and wireless technology. Thus, the communication can be a predefined structure like a regular network or simply an ad hoc communication between at least two devices.

Wi-Fi can allow people to connect to the Internet from the couch at home, the bed in a hotel room, or the conference room at work without wires. Wi-Fi is a wireless technology similar to that used in cell phones, which enables such devices (eg, computers) to send and receive data indoors and outdoors; anywhere within range of a base station. Wi-Fi networks use radio technologies known as IEEE 802.11 (a, b, g, n, ac, ag, etc.) to provide secure, reliable, and fast wireless connections. A Wi-Fi network can be used to connect computers to each other, to the Internet, and to wired networks (which may use IEEE 802.3 or Ethernet). Wi-Fi networks operate in, for example, the unlicensed 2.4GHz and 5GHz radio bands, or have products that include both bands (dual-band), allowing the network to provide connectivity similar to the basic 10BaseT wired Ethernet network used in many offices. real world performance.

FIG. 27 presents an example embodiment 2700 of a mobile network platform 2710 that can implement and utilize one or more aspects of the disclosed subject matter described herein. In one or more embodiments, the mobile network platform 2710 may generate and receive data generated by a base station (e.g., base station equipment 1504, macrocell site 1502, or base station 1614), central office (e.g., central office) associated with the disclosed subject matter. 1501 or 1611) or signals transmitted and received by the transmission device 101 or 102. In general, wireless network platform 2710 may include components that facilitate packet-switched (PS) (e.g., Internet Protocol (IP), Frame Relay, Asynchronous Transfer Mode (ATM)) and circuit-switched (CS) traffic (e.g., voice and data ) both, as well as the components that control the creation of wireless telecommunications for networking, such as nodes, gateways, interfaces, servers or entirely different platforms. As a non-limiting example, wireless network platform 2710 may be included in a telecommunications carrier network, and may be considered a carrier-side component as discussed elsewhere herein. The mobile network platform 2710 includes a CS gateway node(s) 2722, which can interface with data from a network like a telephone network(s) 2740 (e.g., Public Switched Telephone Network (PSTN) or Public Land Mobile CS traffic received by a legacy network (PLMN) or a Signaling System #7 (SS7) network 2770. Circuit-switched gateway node(s) 2722 may authorize and authenticate traffic (eg, voice) originating from such networks. Additionally, CS Gateway node(s) 2722 may access data generated over SS7 network 2770, roaming or mobility; for example, mobility data stored in a Visited Location Register (VLR), which may reside in memory 2730 in. Also, CS gateway node(s) 2722 interfaces CS based traffic and signaling with PS gateway node(s) 2718 . As an example, in a 3GPP UMTS network, the CS gateway node(s) 2722 may be at least partially implemented in a Gateway GPRS Support Node(s) (GGSN). It should be appreciated that the functionality and specific operations of CS gateway node(s) 2722, PS gateway node(s) 2718, and service node(s) 2716 are determined by the mobile network platform for telecommunications Provided and specified by the radio technology(s) used by the 2710.

In addition to receiving and processing CS exchange traffic and signaling, PS gateway node(s) 2718 can also authorize and authenticate PS-based data sessions with served mobile devices. Data sessions may include traffic or content(s) exchanged with networks external to wireless network platform 2710, such as wide area network(s) (WAN) 2750, corporate network(s) 2770, and Service network(s) 2780 , which may be embodied in a local area network (LAN) or interface with mobile network platform 2710 via PS gateway node(s) 2718 . It should be noted that WAN 2750 and enterprise network(s) 2760 may at least partially embody service network(s) like an IP multimedia subsystem (IMS). Based on the radio technology layer(s) available in the technology resource(s) 2717, the packet switching gateway node(s) 2718 can generate a packet data protocol context when a data session is established; Other data structures for routing data can also be generated. To this end, in an aspect, PS gateway node(s) 2718 may include a tunnel interface (e.g., a Tunnel Termination Gateway (TTG) in a 3GPP UMTS network (not shown)) that may facilitate communication with ( Packetized communication of one or more) different wireless networks, such as Wi-Fi networks.

In embodiment 2700, wireless network platform 2710 further includes service node(s) 2716 that transmit Individual packet streams of data streams received by PS gateway node(s) 2718 . It should be noted that for technical resource(s) 2717 that primarily depend on CS communications, server node(s) may route traffic independently of PS gateway node(s) 2718; e.g., The server node(s) may at least partially embody a mobile switching center. As an example, in a 3GPP UMTS network, the serving node(s) 2716 may be embodied in a Serving GPRS Support Node(s) (SGSN).

For radio technologies employing packetized communications, server(s) 2714 in wireless network platform 2710 may execute numerous applications that may generate multiple distinct packetized data streams (streams or flows) and manage (e.g. , scheduling, queuing, formatting...) such streams. Such application(s) may include additional features to the standard services provided by the wireless network platform 2710 (eg, provisioning, billing, customer support . . . ). Data streams (e.g., content(s) as part of a voice call or data session) may be passed to PS gateway node(s) 2718 for authorization/authentication and initiation of the data session, and be Transmitted to service node(s) 2716 for subsequent communication. In addition to application servers, server(s) 2714 may also include utility server(s), which may include provisioning servers, operations and maintenance servers, which may at least partially implement certificate issuance and Security servers with firewalls and other security mechanisms, etc. In one aspect, security server(s) secures communications served over wireless network platform 2710 to act as an authorization and The addition of authentication procedures also ensures the operation and data integrity of the network. Also, provisioning server(s) may provision services from external network(s) such as networks operated by different service providers; for example, WAN 2750 or Global Positioning System(s) (GPS) network (not shown). Provisioning server(s) may also provision coverage through a network associated to wireless network platform 2710 (e.g., deployed and operated by the same service provider), such as that shown in FIG. 1 by providing more network coverage Distributed antenna network for enhanced wireless service coverage. Repeater devices, such as those shown in FIGS. 7 , 8 and 9 , also improve network coverage in order to enhance the subscriber service experience through UE 2775 .

It should be noted that server(s) 2714 may include one or more processors configured to confer at least in part the functionality of macro network platform 2710 . To this end, the one or more processors may execute code instructions stored in memory 2730, for example. It should be appreciated that the server(s) 2714 may include a content manager 2715 that operates in substantially the same manner as previously described.

In example embodiment 2700 , memory 2730 may store information related to the operation of wireless network platform 2710 . Other operational information may include provisioning information, subscriber databases of mobile devices being served through the wireless network platform 2710; application intelligence, pricing schemes such as promotional prices, flat rate schemes, coupon campaigns; telecommunication protocol consistent technical specification(s) for the operation of the layer; etc. Memory 2730 may also store information from at least one of telephone network(s) 2740 , WAN 2750 , corporate network(s) 2770 , or SS7 network 2760 . In one aspect, the memory 2730 can be accessed, for example, as a data storage component or as part of a remotely connected memory store.

In order to provide context for various aspects of the disclosed subject matter, FIG. 27 and the following discussion are intended to provide a brief general description of a suitable environment in which the disclosed subject matter may be implemented. Although the subject matter has been described above in the general context of computer-executable instructions of a computer program that can run on one and/or more computers, those skilled in the art will recognize that the disclosed subject matter can also be combined with other programs. module to implement. Generally, program modules include routines, programs, components, data structures, etc. that perform particular tasks and/or implement particular abstract data types.

FIG. 28 depicts an illustrative embodiment of a communication device 2800. Communications device 2800 may serve as an illustrative embodiment of devices such as mobile devices and in-building devices referenced by the subject disclosure (eg, in FIGS. 15, 16A, and 16B).

Communication device 2800 may include wired and/or wireless transceiver 2802 (herein transceiver 2802), user interface (UI) 2804, power supply 2814, position receiver 2816, motion sensor 2818, orientation sensor 2820, and controller 2806 to Used to manage its operation. The transceiver 2802 may support short-range or long-range wireless access technologies such as WiFi, DECT, or cellular communication technologies, to mention just a few ( and are respectively made by technology alliance and Alliance Registered Trademark). Cellular technologies may include, for example, CDMA-IX, UMTS/HSDPA, GSM/GPRS, TDMA/EDGE, EV/DO, WiMAX, SDR, LTE, and other next generation wireless communication technologies as they emerge. The transceiver 2802 may also be adapted to support circuit-switched wireline access technologies (such as PSTN), packet-switched wireline access technologies (such as TCP/IP, VoIP, etc.), and combinations thereof.

UI 2804 may include a depressible or touch-sensitive keypad 2808 with a navigation mechanism such as a scroll ball, joystick, mouse, or navigation pad for navigating the operation of communication device 2800 . The keyboard 2808 may be an integral part of the housing assembly of the communication device 2800, either via a tethered wired interface (such as a USB cable) or support such as An independent device to which the wireless interface is operatively coupled. Keyboard 2808 may represent a numeric keypad commonly used by telephones, and/or a QWERTY keyboard with alphanumeric keys. UI 2804 may further include a display 2810 such as a monochrome or color LCD (Liquid Crystal Display), OLED (Organic Light Emitting Diode), or other suitable display technology for communicating images to an end user of communication device 2800 . In embodiments where the display 2810 is touch sensitive, some or all of the keyboard 2808 may be presented through the display 2810 with navigation features.

Display 2810 may use touch screen technology to also serve as a user interface for detecting user input. As a touch screen display, the communication device 2800 may be adapted to present a user interface having graphical user interface (GUI) elements selectable by the user with the touch of a finger. Touchscreen display 2810 may be equipped with capacitive, resistive, or other forms of sensing technology in order to detect how much surface area of a user's finger has been placed on a portion of the touchscreen display. This sensory information can be used to control the manipulation of GUI elements or other functions of the user interface. The display 2810 may be an integral part of the housing assembly of the communication device 2800, or a separate device communicatively coupled thereto via a tethered wired interface (such as a cable) or a wireless interface.

The UI 2804 may also include an audio system 2812 that utilizes audio technology to deliver low volume audio (such as near audible to the human ear) and high volume audio (such as a speakerphone for hands-free operation). Audio system 2812 may further include a microphone for receiving audible signals from the end user. Audio system 2812 may also be used for speech recognition applications. The UI 2804 may further include an image sensor 2813, such as a Charge Coupled Device (CCD) camera, for capturing still images or moving images.

Power supply 2814 may utilize common power management techniques such as replaceable and rechargeable batteries, power conditioning techniques, and/or charging system techniques to supply energy to components of communication device 2800 to facilitate long-range or short-range portable communications. Alternatively or in combination, the charging system may utilize an external power source, such as DC power supplied through a physical interface, such as a USB port, or other suitable tethered technology.

The location receiver 2816 may utilize positioning technology, such as a Global Positioning System (GPS) receiver capable of assisting GPS, for identifying the location of the communication device 2800 based on signals generated by a constellation of GPS satellites, which may be used to facilitate location-based services, such as navigation. Motion sensor 2818 may utilize motion sensing technologies such as accelerometers, gyroscopes, or other suitable motion sensing technologies to detect motion of communication device 2800 in three-dimensional space. Orientation sensor 2820 may utilize an orientation sensing technique such as a magnetometer to detect the orientation of communication device 2800 (combined orientations of north, south, west and east, and degrees, minutes, or other suitable orientation metrics).

The communication device 2800 can use the transceiver 2802 to determine the connection with cellular, WiFi, or the proximity of other wireless access points. Controller 2806 may combine computing technology (such as a microprocessor, digital signal processor (DSP), programmable gate array, application specific integrated circuit, and/or video processor) with associated storage memory (such as flash memory, ROM, RAM, SRAM, DRAM, or other storage technologies for executing computer instructions, controlling, and processing data supplied by the aforementioned components of the communication device 2800).

Other components not shown in FIG. 28 may be used in one or more embodiments of the subject disclosure. For example, the communication device 2800 may include a slot for adding or removing an identity module, such as a Subscriber Identity Module (SIM) card or a Universal Integrated Circuit Card (UICC). SIM card or UICC card can be used to identify user services, execute programs, store user data, etc.

In this specification, terms such as "store", "storage", "datastore", "data storage", "database" and basically Any other information storage component related to the operation and function of the component is referred to as a "memory component", or an entity embodied in a "memory" or a component including said memory. It should be appreciated that the memory components described herein can be either volatile memory or nonvolatile memory, or can include both volatile and nonvolatile memory, by way of illustration and not limitation, volatile memory, non-volatile memory, disk storage, and memory storage. In addition, the nonvolatile memory can be included in read only memory (ROM), programmable ROM (PROM), electrically programmable ROM (EPROM), electrically erasable ROM (EEPROM), or flash memory. Volatile memory can include random access memory (RAM), which acts as external cache memory. By way of illustration and not limitation, RAM is available in many forms such as Synchronous RAM (SRAM), Dynamic RAM (DRAM), Synchronous DRAM (SDRAM), Double Data Rate SDRAM (DDR SDRAM), Enhanced SDRAM (ESDRAM), Synchronous Link DRAM (SLDRAM) and Direct High Frequency Dynamic RAM (DRRAM). Furthermore, the memory components of a system or method disclosed herein are intended to include, but are not limited to including, these and any other suitable type of memory.

Moreover, it should be noted that the disclosed subject matter can be practiced with other computer system configurations, including single-processor or multi-processor computer systems, miniature computing devices, mainframe computers, as well as personal computers, handheld computing devices (e.g., PDAs), , telephones, smartphones, watches, tablet computers, netbook computers, etc.), microprocessor-based or programmable consumer or industrial electronics, and more. The illustrated aspects can also be practiced in distributed computing environments where tasks are performed by remote processing devices that are linked through a communications network; however, at least some, if not all aspects of this disclosure can be practiced on stand-alone computers. In a distributed computing environment, program modules may be located in both local and remote memory storage devices.

Some embodiments described herein may also employ artificial intelligence (AI) to facilitate automating one or more of the features described herein. For example, artificial intelligence may be used in optional training controller 230 to evaluate and select candidate frequencies, modulation schemes, MIMO modes, and/or guided wave modes in order to maximize transfer efficiency. Embodiments (eg, related to automatically identifying acquired cell sites that provide the greatest value/benefits after adding to an existing communication network) may employ various AI-based approaches to perform various embodiments thereof. Also, the classifier may be used to determine the acquired ranking or priority of each cell site of the network. The classifier is a function that maps the input attribute vector x=(x1, x2, x3, x4, ..., xn) to the confidence degree (confidence) that the input belongs to a class (class), i.e. f(x)=confidence (class). Such categorization may employ probability-based and/or statistics-based analysis (eg, decomposition into analysis utility and cost) to predict or infer actions that a user desires to be automatically performed. A Support Vector Machine (SVM) is an example of a classifier that may be employed. SVMs operate by finding hypersurfaces in the space of possible inputs that attempt to separate triggering criteria from non-triggering events. Intuitively, this makes the classification correct for test data that is close to but not identical to the training data. Other directed and undirected model classification methods include, for example, Naive Bayes, Bayesian networks, decision trees, neural networks, fuzzy logic models, and probabilistic classification models that provide different modes of independence that can be employed. Classification as used herein also includes statistical regression used to develop priority models.

As will be readily appreciated, one or more embodiments may employ explicit training (e.g., via generic training data) as well as implicit training (e.g., via observing UE behavior, operator preferences, historical information, receiving extrinsic information) classifier. For example, SVMs can be configured via a learning or training phase in the classifier constructor and feature selection module. Accordingly, the classifier(s) may be used to automatically learn and perform a number of functions including, but not limited to, determining which of the acquired cell sites will benefit the greatest number of subscribers and/or the acquired Which of the cell sites will add the least value to the existing communication network coverage, etc.

As used in some contexts in this application, the terms "component," "system," etc., in some embodiments, are intended to refer to or include a computer-related entity or an operating device with one or more specific functions. An associated entity, where an entity may be hardware, a combination of hardware and software, software, or software in execution. As examples, a component may be, but is not limited to being, a process running on a processor, a processor, an object, an executable, a thread of execution, computer-executable instructions, a program, and/or a computer. By way of illustration and not limitation, both an application running on a server and the server can be a component. One or more components can reside within a process and/or thread of execution and a component can be localized on one computer and/or distributed between two or more computers. In addition, these components can execute from various computer readable media having various data structures stored thereon. These components may communicate via local and/or remote processes, such as by having one or more data packets (e.g., from via A signal of data from one component interacting with another component). As another example, a component may be a device having a specific function provided by a mechanical part operated by circuitry or electronic circuitry operated by a software or firmware application executed by a processor, where the processor may operate on internal or external to the device and executes at least a portion of a software or firmware application. As yet another example, a component may be a device that provides specific functionality through an electronic component without mechanical parts, which may include a processor therein to execute software or firmware that at least partially renders the electronic component functional. While various components are shown as separate components, it should be appreciated that multiple components may be implemented as a single component, or a single component may be implemented as multiple components, without departing from example embodiments.

Additionally, the various embodiments can be implemented as a method, apparatus, or article of manufacture using standard programming and/or engineering techniques to produce software, firmware, hardware, or any combination thereof to control a computer to implement the disclosed subject matter. As used herein, the term "article of manufacture" is intended to cover a computer program accessible from any computer-readable device or computer-readable storage/communication medium. For example, computer readable storage media may include, but is not limited to, magnetic storage devices (e.g., hard disk, floppy disk, magnetic stripe), optical disks (e.g., compact disk (CD), digital versatile disk (DVD)), smart cards, and flash memory devices ( For example, card, stick, key drive). Of course, those skilled in the art will recognize many modifications may be made to this configuration without departing from the scope or spirit of the various embodiments.

Additionally, the words "example" and "exemplary" are used herein to mean serving as an example or illustration. Any embodiment or design described herein as "example" or "exemplary" is not necessarily to be construed as preferred or advantageous over other embodiments or designs. Rather, use of the word example or exemplary is intended to present concepts in a concrete manner. As used in this application, the term "or" is intended to mean an open "or" rather than an exclusive "or". That is, unless specified otherwise or clear from context, "X employs A or B" is intended to refer to any natural inclusive permutation. That is, if X employs A; X employs B; or X employs both A and B, then "X employs A or B" is satisfied in any of the above cases. Furthermore, as used in this application and the appended claims, unless specified otherwise or clear from the context to be directed to a singular form, "a (a)" and "an (an)" shall be generic is construed to mean "one or more".

Furthermore, terms such as "user equipment", "mobile station", "mobile telephone", "subscriber station", "access terminal", "terminal", "handset", "mobile device" (and/or terms denoting similar The term) may refer to a wireless device used by a subscriber or user of a wireless communication service to receive or transmit data, control, voice, video, sound, gaming, or substantially any data or signaling stream. The foregoing terms are used interchangeably herein and with reference to the associated figures.

Furthermore, the terms "user," "subscriber," "customer," "consumer," etc. may be used interchangeably throughout unless the context warrants a specific distinction between these terms. It should be appreciated that such terms may refer to human entities or automated components supported by artificial intelligence (e.g., the ability to make inferences based at least on complex mathematical formalisms) that may provide simulated vision, voice recognition, etc. .

As used herein, the term "processor" may refer to substantially any computing processing unit or device, including, but not limited to, single-core processors; single processors with software multi-threaded execution capabilities; multi-core processors; Multi-core processors with multi-threaded execution capabilities; multi-core processors with hardware multi-threading technology; parallel platforms; and parallel platforms with distributed shared memory. Additionally, a processor may refer to an integrated circuit, application specific integrated circuit (ASIC), digital signal processor (DSP), field programmable gate array (FPGA), programmable logic controller (PLC) designed to perform the functions described herein. , complex programmable logic device (CPLD), discrete gate or transistor logic, discrete hardware components, or any combination thereof. Processors can utilize nanoscale architectures such as but not limited to molecular and quantum dot based transistors, switches and gates in order to optimize the use of space or enhance the performance of user equipment. A processor may also be implemented as a combination of computing processing units.

As used herein, terms such as "data storage", "data storage", "database" and substantially any other information storage component related to the operation and function of the component Both refer to a "memory component" or an entity embodied in a "memory" or a component comprising a memory. It should be appreciated that the memory components or computer readable storage media described herein can be either volatile memory or nonvolatile memory, or can include both volatile and nonvolatile memory.

What has been described above includes only examples of various embodiments. It is, of course, not possible to describe every conceivable combination of components or methodologies for purposes of describing these embodiments, but one of ordinary skill in the art will recognize that many further combinations and permutations of the given embodiments are possible. Accordingly, the embodiments disclosed and/or claimed herein are intended to embrace all such alterations, modifications and variations that fall within the spirit and scope of the claims. Furthermore, to the extent the term "includes" is used in the detailed description or claims, such term is intended to be inclusive in a manner similar to the term "comprising", as when " "comprising" is to be construed when used as a transitional word in a claim.

Additionally, flowcharts may include "start" and/or "continue" indications. The "start" and "continue" directions reflect that the steps presented may optionally be incorporated into or otherwise used with other routines. In this context, "beginning" indicates the beginning of a given first step and may be preceded by other activities not specifically shown. Further, the "continue" indication reflects that the presented steps may be performed multiple times and/or may be followed by other activities not specifically shown. Additionally, while the flowcharts indicate a particular ordering of steps, other orderings are possible so long as the principle of causality is maintained.

As may also be used herein, the term(s) "operably coupled to", "coupled to" and/or "coupled" includes direct coupling between items and/or between items via one or more Indirect coupling of intermediate terms. These items and intermediate items include, but are not limited to, contacts, communication paths, components, circuit elements, circuits, functional blocks, and/or devices. As an example of indirect coupling, a signal transmitted from a first item to a second item may be modified by one or more intermediate items modifying the form, nature, or format of information in the signal, while one or more elements of the information in the signal Still delivered in a way that can be recognized by the second item. In another example of indirect coupling, an action in a first item may cause a reaction in a second item as a result of actions and/or reactions in one or more intermediate items.

Although specific embodiments have been illustrated and described herein, it should be appreciated that any arrangement, which achieves the same or a similar purpose, may be substituted for the embodiments described or illustrated in the subject disclosure. This subject disclosure is intended to cover any and all adaptations or variations of various embodiments. Combinations of the above embodiments, as well as other embodiments not specifically described herein, may be used in the subject disclosure. For example, one or more features from one or more embodiments may be combined with one or more features from one or more other embodiments. In one or more embodiments, positively referenced features may also be negatively referenced and excluded from embodiments where they may or may not be replaced by another structural and/or functional feature. The steps or functions described with respect to the embodiments of the subject disclosure may be performed in any order. Steps or functions described with respect to embodiments of the subject disclosure may be performed alone or in combination with other steps or functions of the subject disclosure, as well as other steps from other embodiments or not yet described in the subject disclosure. Furthermore, more or less than all features described with respect to the embodiments may also be utilized.

Claims (15)

1. a kind of method, including：

Multiple transmitters of transmitting station are configured to generate electromagnetic wave, wherein the electromagnetic wave is modulated for transmitting communication data； And

Inducted on the outer surface of transmission medium the electromagnetic wave according to target field structure by the transmitting station, wherein the mesh Mark field structure includes at least part electric field with spacial alignment of the electromagnetic wave, at least one described in the electromagnetic wave Partial electric-field when crossing the substance being arranged on the outer surface of the transmission medium on the electromagnetic wave propagation direction, The spacial alignment reduces the electromagnetic wave propagation loss.

2. the method for claim 1, wherein the target field structure is described by being inducted according to transverse magnetic wave pattern Electromagnetic wave is realized.

3. method as claimed in claim 2, wherein the transverse magnetic wave pattern includes TM0m wave modes, and wherein, m is big In 0.

4. the method for claim 1, wherein the target field structure is by being inducted the electricity according to mixing wave mode Magnetic wave is realized.

5. method as claimed in claim 4, wherein the mixing wave mode includes EH1m wave modes, and wherein, m is more than 0。

6. method as claimed in claim 4, wherein the mixing wave mode includes HE2m wave modes, and wherein, m is more than 1。

7. the method for claim 1, wherein the electromagnetic wave has the cutoff frequency more than 0 hertz.

8. the method for claim 1, wherein the multiple transmitter of configuration by the transmitting station in response to connecing Having for receiving is carried out with Signal Degrade is detected in another electromagnetic wave of the different field structure of target field structure, In, the substance includes liquid, and wherein, and the transmission medium includes insulated electric conductor or promotes to be coupled to dielectric day Line is to radiate the dielectric core of wireless signal.

9. the method for claim 1, wherein the spacial alignment of at least part electric field substantially not with institute The outer surface of transmission medium is stated into azimuth.

10. the method for claim 1, wherein the spacial alignment of at least part electric field substantially not with The outer surface of the transmission medium is longitudinally aligned.

11. the method for claim 1, wherein the multiple transmitter of configuration makes the multiple transmitter generate Respectively multiple wireless signals with target phase, the multiple wireless signal combination is to form the institute with the spacial alignment State electromagnetic wave.

12. a kind of transmitting station, including：

Multiple transmitters；And

Circuit is coupled to the multiple transmitter,

Wherein, the circuit execution includes the operation of the following terms：

The multiple transmitter is configured to generate electromagnetic wave, wherein the electromagnetic wave is modulated for transmitting communication data；And

Inducted on the outer surface of transmission medium the electromagnetic wave according to target field structure, wherein the target field structure includes At least part electric field with spacial alignment of the electromagnetic wave, when at least part electric field of the electromagnetic wave is in institute When stating the substance for crossing and being arranged on the outer surface of the transmission medium on electromagnetic wave propagation direction, the spacial alignment Reduce the electromagnetic wave propagation loss.

13. transmitting station as claimed in claim 12, wherein the target field structure is by being inducted according to transverse magnetic wave pattern The electromagnetic wave is realized.

14. transmitting station as claimed in claim 12, wherein the target field structure is by being inducted institute according to mixing wave mode Electromagnetic wave is stated to realize.

15. transmitting station as claimed in claim 14, wherein the mixing wave mode includes EH1m wave modes, and wherein, m More than 0, and wherein, the mixing wave mode includes HE2m wave modes, and wherein, and m is more than 1.